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8/2/2019 Static Cmos
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DESIGNING OF COMBINATIONAL
LOGIC GATES IN CMOS
G.SUSMITHA
ROLL NO:06
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COMBINATIONAL VS. SEQUENTIAL LOGIC
CombinationalLogicCircuit
Out In Combinational
LogicCircuit
Out In
State
Combinational Sequential
Output = f (In) Output = F(In, Previous In)
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STATIC CMOS CIRCUIT
At every point in time (except during the switchingtransients) each gate output is connected to eitherV DD or V ss via a low-resistive path.
The outputs of the gates assume at all times the valueof the Boolean function, implemented by the circuit
This is in contrast to the dynamic circuit class, whichrelies on temporary storage of signal values on thecapacitance of high impedance circuit nodes.
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STATIC COMPLEMENTARY CMOS
F(In1,In2,InN)
In1In2
InN
In1In2InN
PUN
PDN
PMOS only
NMOS only
PUN and PDN are dual logic networks
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NMOS TRANSISTORS
IN SERIES/PARALLEL CONNECTIONTransistors can be thought as a switch controlled by its gate signal
NMOS switch closes when switch control input is high
X Y
A B
Y = X if A and B
XY
A
B Y = X if A OR B
NMOS Transistors pass a strong 0 but a weak 1
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PMOS TRANSISTORS
IN SERIES/PARALLEL CONNECTION
X Y
A B
Y = X if A AND B = A + B
X Y
A
B Y = X if A OR B = AB
PMOS Transistors pass a strong 1 but a weak 0
PMOS switch closes when switch control input is low
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THRESHOLD DROPS
VDD 0PDN
CL VDD CL
S
SD
D
VGS
0 VDD
PUN
0 VDD
- VTn
VDD |VTp |
VDD
0 VDD
CL
S
D
CL
VDD
VDD
S
D
VGS
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COMPLEMENTARY CMOS LOGIC STYLE
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COMPLEX CMOS GATE
D
A
B C
D
AB
C
OUT = D + A (B + C)
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CONSTRUCTING A COMPLEX GATE
C
(a) pull-down network
SN1 SN4
SN2
SN3 D
F F
A
D B
C
D
F
A
B
C
(b) Deriving the pull-up network hierarchically by identifyingsub-nets
D
A
A
B
C
V DD V DD
B
(c) complete gate
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C
A B
X = C (A + B)
B
AC
i
j
ABC
Logic Graph
j
VDDX
X
i
GND
AB
C
PUN
PDN
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C
A B
X = (A+B)(C+D)
B
A
D
VDDX
X
GND
AB
C
PUN
PDN
C
D
D
ABCD
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EXAMPLE: X = AB+CD
GND
x
a
b c
d
V DD x
GND
x
a
b c
d
V D D x
(a) Logic graphs for ( ab+cd ) (b) Euler Paths { a b c d }
a c d
x
V D D
GND
(c) stick diagram for ordering {a b c d }
b
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PROPERTIES OF COMPLEMENTARY CMOSGATES:
High noise margins :V OH and V OL are at V DD and GND , respectively.
No static power consumption : There never exists a direct path between V DD andV SS ( GND ) in steady-state mode .
Comparable rise and fall times: (under appropriate sizing conditions)
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SWITCH DELAY MODEL
AReq
A
Rp
A
Rp
A
Rn CL
A
CL
B
Rn
A
Rp
B
Rp
A
Rn C int
B
Rp
A
Rp
A
Rn
B
Rn CL
C int
INV
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INPUT PATTERN EFFECTS ON DELAY
Delay is dependent onthe pattern of inputs
Low to high transition both inputs go low
delay is 0.69 R p /2 CL one input goes low
delay is 0.69 R p CL
High to low transition both inputs go high
delay is 0.69 2Rn CL
CL B
Rn
A
Rp
B
Rp
A
Rn C int
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TRANSISTOR SIZING
CL
B
Rn
A
Rp
B
Rp
A
Rn Cint
B
Rp
A
Rp
A
Rn
B
Rn CL
C int 2
2
2 2
1 1
4
4
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FAN-IN CONSIDERATIONS
DCBA
D
C
B
A CL
C3
C2
C1
Distributed RC model(Elmore delay)
tpHL = 0.69 R eqn (C1+2C 2+3C 3+4C L)
Propagation delay deteriorates rapidly as afunction of fan-in quadratically in the worstcase.
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Fast Complex Gates:Design Technique 1
Transistor sizing as long as fan-out capacitance dominates
Progressive sizing
InN CL
C3
C2
C1 In1
In2
In3
M1
M2
M3
MN Distributed RC line
M1 > M2 > M3 > > MN (the fet closest to the
output is the smallest)
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FAST COMPLEX GATES:DESIGN TECHNIQUE 2Transistor ordering
C2
C1 In1
In2
In3
M1
M2
M3 CL
C2
C1 In3
In2
In1
M1
M2
M3 CL
critical path critical path
charged1
0 1 charged
charged1
delay determined by time todischarge C L, C 1 and C 2
delay determined by time todischarge C L
1
1
0 1
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FAST COMPLEX GATES:DESIGN TECHNIQUE 3
F = ABCDEFGH
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Delay in a Logic Gate
Gate delay:
d = h + p
effort delay intrinsic delay
Effort delay:
h = g f
logical effort effective fanout = C out /C in
Logical effort is a function of topology, independent of sizingEffective fanout (electrical effort) is a function of load/gate size
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LOGICAL EFFORT
f g pC C
C Rk Delayin
Lunit unit
1
g logical effort ,which is defined as how much moreinput capacitance a gate presents to deliver the sameoutput current as inverter.
P-intrincsic delay:ratio of intrinsic delays of gate andinverter
F-effective fanout
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EXAMPLES OF LOGICAL EFFORT
B
A
A B
F
V DDV DD
A B
A
B
F
V DD
A
F
1
2 2 2
2
2
1 1
4
4
Inverter 2-input NAND 2-input NOR
g = 1 g = 4/3 g = 5/3
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LOGICAL EFFORT OF GATES
IntrinsicDelay
EffortDelay
1 2 3 4 5
Fanout f
1
2
3
4
5
I n v e r t e
r : g =
1 ; p =
1
2 - i n p u t
N A N D
:g = 4 / 3
; p = 2
N o r m a l i z e d D e l a y
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LOGICAL EFFORT OF COMMON LOGIC GATES
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MULTISTAGE NETWORKS
N i
iii f g p Delay1
Stage effort: h i = g ifi
Path electrical effort: F = C out /C in
Path logical effort: G = g 1g2g N
Branching effort: B = b 1b2b N
Path effort: H = GFB
Path delay D = S d i = S p i + S h i
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BRANCHING EFFORT
Branching effort:
pathon
pathoff pathon
C
C C b
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OPTIMUM EFFORT PER STAGE
H h N When each stage bears the same effort:
N H h
P NH p f g D N iii / 1
Minimum path delay
Effective fanout of each stage: ii gh f
Stage efforts: g 1f1 = g 2f2 = = g NfN
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Example: Optimize Path
g = 1f = a g = 5/3
f = b/a
g = 5/3f = c/b
g = 1
f = 5/c
1a
b c
5
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EXAMPLE 8-INPUT AND
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RATIOED LOGIC
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IMPROVED LOADS
V DD
V SS
PDN1
Out
V DD
V SS
PDN2
Out
A A B B
M1 M2
Differential Cascode Voltage Switch Logic (DCVSL)
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DCVSL EXAMPLE
B
A A
B B B
Out
Out
XOR-NXOR gate
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PASS-TRANSISTOR LOGIC
I n p u t s
Switch
Network
Out Out
A
B
B
B
N transistors
No static consumption
Pass transistors require low switching energy to chargeup a node due to the reduced voltage swing
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EXAMPLE: AND GATE
B
B
F = AB
0
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DIFFERENTIAL PASS TRANSISTOR LOGIC
A
B
A
B
B B B B
A
B
A
B
F=AB
F=AB
F=A+B
F=A+B
B B
A
A
A
A
F=A
F=A
OR/NOR EXOR/NEXORAND/NAND
F
F
Pass-TransistorNetwork
Pass-TransistorNetwork
AABB
AABB
Inverse
(a)
(b)
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NMOS ONLY LOGIC:LEVEL RESTORING TRANSISTOR
M 2
M 1
M n
M r
Out A
B
V DD V DD Level Restorer
X
Advantage: Full Swing
Ratio problem
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TRANSMISSION GATE
A B
C
C
A B
C
C
B
C L
C = 0 V
A = 2.5 V C = 2.5 V
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TRANSMISSION GATE BASEDMULTIPLEXER
AM 2
M 1
B
S
S
S F
V DD
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TRANSMISSION GATE XOR
A
B
F
B
A
B
B M1
M2
M3/M4
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V out
0 V
2.5 V
2.5 VR n
R p
0.0 1.0 2.00
10
20
30
V out , V
essance,oms
R n
R p
R n || R p
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DELAY IN TRANSMISSION GATE NETWORKS
V 1 V i-1
C
2.5 2.5
0 0
V i V i+1
C C
2.5
0
V n-1 V n
C C
2.5
0
In
V 1 V i V i+1
C
V n-1 V n
C C
In R eq R eq R eq R eq
C C
(a)
(b)
C
R eq R eq
C C
R eq
C C
R eq R eq
C C
R eq
C In
m
(c)
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PROS AND CONS:
Pros:Robustnessgood performanceNo Static Power Dissipation
Cons:
Requires 2N transistors with a fan in ofN
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CONCLUSION:
Static CMOS circuits can be used for devicesthat have no extreme area,complexity or
speedconstraints
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REFERENCES:
1.DIGITAL INTEGRATED CIRCUTS BYJAN RABAEY,ANANTHA CHANDRAKASAN,BORIVOJE NIKOLIC
2.http://bwrc.eecs.berkeley.edu/ICbook
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THANK U