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1
Radar Measurements II
Chris Allen ([email protected])
Course website URL people.eecs.ku.edu/~callen/725/EECS725.htm
2
Ground imaging radarIn a real-aperture system images of radar backscattering are mapped into slant range, R, and along-track position.
The along-track resolution, y, is provided solely by the antenna. Consequently the along-track resolution degrades as the distance increases. (Antenna length, ℓ, directly affects along-track resolution.)
Cross-track ground range resolution, x, is incidence angle dependent
]m[Ry az
]m[sin2
cx p
where p is the compressed
pulse duration
y
xx
along-trackdirection
cross-trackdirection
cross-trackdirection
slant range
ground rangeground range
slant range
R
3
Slant range vs. ground rangeCross-track resolution in the ground plane (x) is theprojection of the range resolution from the slant planeonto the ground plane.
At grazing angles ( 90°), r x
At steep angles ( 0°), x For = 5°, x = 11.5 r
For = 15°, x = 3.86 r
For = 25°, x = 2.37 r
For = 35°, x = 1.74 r
For = 45°, x = 1.41 r
For = 55°, x = 1.22 r
4
Real-aperture, side-looking airborne radar (SLAR) image of Puerto Rico
Mosaicked image composed of 48-km (30-mile) wide strip map imagesRadar parametersmodified Motorola APS-94D systemX-band (3-cm wavelength)altitude: 8,230 m (above mean sea level)azimuth resolution: 10 to 15 m
~ 40 x 100 milesDigital Elevation Model of Puerto Rico
5
Another SLAR image
SLAR operator’s console
5-m (18 feet) SLAR antenna mounted beneath fuselage
X-band systemCivilian uses include:• charting the extent of flood waters,• mapping, locating lost vessels,• charting ice floes,• locating archaeological sites,• seaborne pollution spill tracking,• various geophysical surveying chores.
SLAR image of river valley
6
Limitations of real-aperture systemsWith real-aperture radar systems the azimuth resolution depends on the antenna’s azimuth beamwidth (az) and the slant range, R
Consider the AN/APS 94 (X-band, 5-m antenna length) az = 6 mrad or 0.34
For a pressurized jet aircraftaltitude of 30 kft (9.1 km) and an incidence angle of 30 for a slant range of 10.5 km
R = h/cos = 9100 / cos 30 = 10500 m
y = 63 m (coarse but useable)
Now consider a spaceborne X-band radar (15-m antenna length) az = 2 mrad or 0.11500-km altitude and a 30 incidence angle (27.6 look angle) for a 570.5-km slant range
y = 1.1 km (very coarse)
The azimuth resolution of real-aperture radar systems is very coarse for long-range applications
]m[Ry az
7
Radar equation for extended targetsSince A = x y we have
Substituting these terms into the range equation leads to
note the range dependence is now R-3 whereas for a point target it is R-4
This is due to the fact that a larger area is illuminated as R increases.
R
sin2
c
R4
GP
R4
AGPP az
p
43
2t
2
43
2t
2
r
Rsin2
cA az
p
33
paz2
t2
rR4sin2
cGPP
8
SNR and the radar equationNow to consider the SNR we must use the noise power
PN = kT0BF
Assuming that terrain backscatter, , is the desired signal (and not
simply clutter), we get
Solving for the maximum range, Rmax, that will yield the minimum
acceptable SNR, SNRmin, gives
FBTkR4sin2
cGPSNR
033
paz2
t2
3
0min3
paz2
t2
maxFBTkSNR4sin2
cGPR
9
Radar altimetryAltimeter – a nadir-looking radar that precisely measures the range to the terrain below. The terrain height is derived from the radar’s position.
c p/ 2
H
10
Altimeter dataRadar map of the contiguous 48 states.
11
Altimeter
12
TOPEX/PoseidonA - MMS multimission platform
B - Instrument module 1/Data transmission TDRS 2/Global positioning system antenna 3/Solar array 4/Microwave radiometer 5/Altimeter antenna 6/Laser retroreflectors 7/DORIS antenna
Dual frequency altimeter (5.3 and 13.6 GHz)
operating simultaneously.Three-channel radiometer (18, 21, 37 GHz) provides water vapor data beneath satellite (removes ~ 1 cm uncertainty).
2-cm altimeter accuracy100 million echoes each day10 MB of data collected per day
French-American systemLaunched in 199210-day revisit period (66 orbit inclination)
Altitude: 1336 kmMass: ~ 2400 kg
13
Altimeter data
Global topographic map of ocean surface produced with satellite altimeter.
14
Altimeter data
15
Mars Orbiter Laser Altimeter (MOLA)Laser altimeter (not RF or microwave)Launched November 7, 1996
Entered Mars orbit on September 12, 1997
Selected specifications282-THz operating frequency (1064-nm wavelength)
10-Hz PRF
48-mJ pulse energy
50-cm diameter antenna aperture (mirror)
130-m spot diameter on surface
37.5-cm range measurement resolution
16
Mars Orbiter Laser Altimeter (MOLA)
17
Radar altimetryThe echo shape, E(t), of altimetry data is affected by the radar’s point target response, p(t), it’s flat surface response, S(t), which includes gain and backscatter variations with incidence angle, and the rms surface height variations, h(t).
Analysis of the echo shape, E(t), can provide insight regarding the surface. From the echo’s leading we learn about the surface height variations, h(t), and from its trailing edge we learn about the backscattering characteristics, ().
18
Signal integrationCombining consecutive echo signals can improve the signal-to-noise ratio (SNR) and hence improve the measurement accuracy, or it can improve our estimate of the SNR and hence improve our measurement precision.
Two basic schemes for combining echo signals in the slow-time dimension will be addressed.
Coherent integration
Incoherent integration
Coherent integration (also called presumming or stacking) involves working with signals containing magnitude and phase information (complex or I & Q values, voltages, or simply signals that include both positive and negative excursions)
Incoherent integration involves working with signals that have been detected (absolute values, squared values, power, values that are always positive)
Both operations involve operations on values expressed in linear formats and not expressed in dB.
19
Coherent integrationCoherent integration involves the summation or averaging of multiple echo signal records (Ncoh) along the slow-time dimension.Coherent integration is commonly performed in real time during radar operation.
+ + +…+ =F
ast tim
e
Pulse echo
#1
Pulse echo
#2
Pulse echo
#3
Pulse echo #Ncoh
Coherently integrated
record
1 1 1 1 Ncoh
Coherent integration affects multiple radar parameters.
It reduces the data volume (or data rate) by Ncoh.
It improves the SNR of in-band signals by Ncoh.
It acts as a low-pass filter attenuating out-of-band signals.
20
Coherent integration
21
Coherent integration
22
Coherent integrationSignal power found using
where vs is the signal voltage vector
Noise power found using
where vs+n is the signal + noise voltage vector
SNR is then
note that [std_dev]2 is variance
2ss )v(dev_stdP
s2
nsn P)v(dev_stdP
ns PPSNR
23
Coherent integrationSumming Ncoh noisy echoes has the following effect
Signal amplitude is increased by Ncoh
Signal power is increased by (Ncoh)2
Noise power is increased by Ncoh
Therefore the SNR is increased by Ncoh
Noise is uncorrelated and therefore only the noise power adds whereas the signal is correlated and therefore it’s amplitude adds. This is the power behind coherent integration.
Averaging Ncoh noisy echoes has the following effectSignal amplitude is unchangedSignal power is unchangedNoise power is decreased by Ncoh
Therefore the SNR is increased by Ncoh
Noise is uncorrelated and has a zero mean value.Averaging Ncoh samples of random noise reduces its variance by Ncoh and hence the noise power is reduced.
24
Coherent integrationUnderlying assumptions essential to benefit from coherent integration.
Noise must be uncorrelated pulse to pulse.Coherent noise (such as interference) does not satisfy this requirement.
Signal must be correlated pulse to pulse.That is, for maximum benefit the echo signal’s phase should vary by less than 90 over the entire integration interval.
For a stationary target relative to the radar, this is readily achieved.
For a target moving relative to the radar, the maximum integration interval is limited by the Doppler frequency. This requires a PRF much higher than PRFmin, that is the Doppler signal is significantly oversampled.
Ncoh = 10
-1.2
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
1.2
0 1 2 3 4 5time (ms)
Sig
nal
(V
)
400-Hz 10-kHz samples
-1.2
-1
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
1
1.2
0 1 2 3 4 5time (ms)
Sig
nal
(V
)
400-Hz 1-kHz samples
25
Coherent integrationCoherent integration filters data in slow-time dimension.Filter characterized by its transfer function.
26
Coherent integrationImpact on SNR
Coherent integration improves the SNR by Ncoh.
For point targets
For extended targets
vidcoh
033
cohpaz22
tcoh SNRN
FBTkR4sin2
NcGPSNR
vidcoh
043
coh22
tcoh SNRN
FBTkR4
NGPSNR
SNRcoh
SNRvid
27
Coherent integrationSo what is going on to improve the SNR ?
Is the receiver bandwidth being reduced ? No
By coherently adding echo signal energy from consecutive pulses we are effectively increasing the illumination energy.
This may be thought of as increasing the transmitted power, Pt.
Again returning to the ACR 430 airfield-control radar exampleThe transmitter has peak output power, Pt, of 55 kW and a pulse duration, , of 100 ns, (i.e., B = 10 MHz).
Hence the transmit pulse energy is Pt = 5.5 mJ
Coherently integrating echoes from 10 pulses (Ncoh = 10) produces an SNR equivalent to the case where Pt is 10 times greater, i.e., 550 kW and the total illumination energy is 55 mJ.
Alternatively, coherent integration permits a reduction of the transmit pulse power, Pt, equivalent to the Ncoh while retaining a constant SNR.
TxnSn = 1
NcohPt
Tx
NcohPt
28
Incoherent integrationIncoherent detection is similar to coherent detection in that it involves the summation or averaging of multiple echo signal records (Ninc) along
the slow-time dimension.
Prior to integration the signals are detected (absolute values, squared values, power, values that are always positive).
Consequently the statistics describing the process is significantly more complicated (and beyond the scope of this class).
The improvement in signal-to-noise ratio due to incoherent integration varies between Ninc and Ninc, depending on a variety of parameters
including detection process and Ninc.
How it works: For a stable target signal, the signal power is fairly constant while the noise power fluctuates. Therefore integration consistently builds up the signal return whereas the variability of the noise power is reduced. Consequently the detectability of the signal is improved.
29
Incoherent integrationExample using square-law detection
30
2200
2300
2400
2500
2600
2700
2800
2900
3000
-2000 -1500 -1000 -500 0 500 1000 1500 2000X (m)
Ran
ge
(m)
5,280,000
5,480,000
5,680,000
5,880,000
6,080,000
6,280,000
6,480,000
6,680,000
6,880,000
7,080,000
Sig
nal
ph
ase
(deg
)
More on coherent integrationClearly coherent integration offers tremendous SNR improvement.To realize the full benefits of coherent integration the underlying assumptions must be satisfied
Noise must be uncorrelated pulse to pulseSignal phase varies less than 90 over integration interval
The second assumption limits the integration interval for cases involving targets moving relative to the radar.
Coherent integration can be used if phase variation is removed first.Processes involved include range migration and focusing.For a 2.25-kHz PRF, Ncoh = 100,000 or 50 dB of SNR improvement
[deg]R2
360
v
x
-y
z
H
flight path
ground track
target
offset
(0,0,0)R2 km
1 km
= 30 cm
90 m/s
31
Tracking radarIn this application the radar continuously monitors the target’s range and angular position (angle-of-arrival – AOA).
Tracking requires fine angular position knowledge, unlike the search radar application where the angular resolution was el and az.
Improved angle information requires additional information from the antenna.
Monopulse radarWith monopulse radar, angular position measurements are accomplished with a single pulse (hence the name monopulse).This system relies on a more complicated antenna system that employs multiple radiation patterns simultaneously.
There are two common monopulse varieties• amplitude-comparison monopulse
• phase-comparison monopulseEach variety requires two (or more) antennas and thus two (or more) receive channels
32
Amplitude-comparison monopulseThis concept involves two co-located antennas with slightly shifted pointing directions.The signals output from the two antennas are combined in two different processesS (sum) output is formed by summing the two antenna signals (difference) output is formed by subtracting signals from one anotherThese combinations of the antenna signals produce corresponding radiation patterns (S and ) that have distinctly different characteristics/S (computed in signal processor) provides an amplitude-independent estimate of the variable related to the angle
33
Phase-comparison monopulseThis concept involves two antennas separated by a small distance d with parallel pointing directions.The received signals are compared to produce a phase difference, , that yields angle-of-arrival information.
For small , sin
]rad[sind2
]rad[d2
d2
34
Dual-axis monopulseBoth amplitude-comparison and phase-comparison approaches provide angle-of-arrival estimates in one-axis.
For dual-axis angle-of-arrival estimation, duplicate monopulse systems are required aligned on orthogonal axes.
35
Dual-axis monopulse
36
MonopulseConventional monopulse processing to obtain the angle-of-arrival is valid for only one point target in the beam, otherwise the angle estimation is corrupted.
Other more complex concepts exist for manipulating the antenna’s spatial coverage.
Theses exploit the availability of signals from spatially diverse antennas (phase centers).
Rather than combining these signals in the RF or analog domain, these signals are preserved into the digital domain where various antenna patterns can be realized via ‘digital beamforming.’
37
Frequency agilityFrequency agility involves changing the radar’s operating frequency on a pulse-to-pulse basis. (akin to frequency hopping in some wireless communication schemes)
AdvantagesImproved angle estimates (refer to text for details)Reduced multipath effectsLess susceptibility to electronic countermeasuresReduced probability detection, low probability of intercept (LPI)
DisadvantagesScrambles the target phase informationChanging f changes To undo the effects of changes in f requires precise knowledge of R
Pulse-to-pulse frequency agility is typically not used in coherent radar systems.
]rad[c
fR4R22
38
Pulse compressionPulse compression is a very powerful concept or technique permitting the transmission of long-duration pulses while achieving fine range resolution.
39
Pulse compressionPulse compression is a very powerful concept or technique permitting the transmission of long-duration pulses while achieving fine range resolution.
Conventional wisdom says that to obtain fine range resolution, a short pulse duration is needed.However this limits the amount of energy (not power) illuminating the target, a key radar performance parameter.Energy, E, is related to the transmitted power, Pt by
Therefore for a fixed transmit power, Pt, (e.g., 100 W), reducing the pulse duration, , reduces the energy E.
Pt = 100 W, = 100 ns R = 50 ft, E = 10 JPt = 100 W, = 2 ns R = 1 ft, E = 0.2 J
Consequently, to keep E constant, as is reduced, Pt must increase.
0 t dttPE
Pt
40
More Tx power??Why not just get a transmitter that outputs more power?
High-power transmitters present problemsRequire high-voltage power supplies (kV)
Reliability problems
Safety issues (both from electrocution and irradiation)
Bigger, heavier, costlier, …
41
Simplified view of pulse compression
Energy content of long-duration, low-power pulse will be comparable to that of the short-duration, high-power pulse
1 « 2 and P1 » P2
time
1
Po
we r
P1
P2
2
2211 PP Goal:
42
Pulse compressionRadar range resolution depends on the bandwidth of the received signal.
The bandwidth of a time-gated sinusoid is inversely proportional to the pulse duration.So short pulses are better for range resolution
Received signal strength is proportional to the pulse duration.So long pulses are better for signal reception
Solution: Transmit a long-duration pulse that has a bandwidth corresponding to that of a short-duration pulse
c = speed of light, R = range resolution, = pulse duration, B = signal bandwidth
B2
c
2
cR
43
Pulse compression, the compromiseTransmitting a long-duration pulse with a wide bandwidth requires modulation or coding the transmitted pulseto have sufficient bandwidth, B
can be processed to provide the desired range resolution, R
Example:Desired resolution, R = 15 cm (~ 6”) Required bandwidth, B = 1 GHz (109 Hz)
Required pulse energy, E = 1 mJ E(J) = Pt(W)· (s)
Brute force approach
Raw pulse duration, = 1 ns (10-9 s) Required transmitter power, Pt = 1 MW !
Pulse compression approach
Pulse duration, = 0.1 ms (10-4 s) Required transmitter power, Pt = 10 W
44
The long-duration pulse is coded to have desired bandwidth.There are various ways to code pulse.
Phase code short segmentsEach segment duration = 1 ns
Linear frequency modulation (chirp)
for 0 t fC is the starting frequency (Hz)k is the chirp rate (Hz/s)B = k = 1 GHz
Choice driven largely by required complexity of receiver electronics
Pulse coding
C2
C tk5.0tf2cosA)t(s
1 ns
45
Phase coded waveform
46
Analog signal processing
47
Binary phase coding
48
Receiver signal processingphase-coded pulse compression
Correlation process may be performed in the analog or digital domain. A disadvantage of this approach is that the data acquisition system (A/D converter) must operate at the full system bandwidth (e.g., 1 GHz in our example).
PSL: peak sidelobe level (refers to time sidelobes)
time
49
Binary phase codingVarious coding schemes
Barker codesLow sidelobe level
Limited to modest lengths
Golay (complementary) codesCode pairs – sidelobes cancel
Psuedo-random / maximal length sequential codesEasily generated
Very long codes available
Doppler frequency shifts and imperfect modulation (amplitude and phase) degrade performance
50
Chirp waveforms and FM-CW radarTo understand chirp waveforms and the associated signal processing, it is useful to first introduce the FM-CW radar.
FM – frequency modulation
CW – continuous wave
This is not a pulsed radar, instead the transmitter operates continuously requiring the receiver to operate during transmission.
Pulse radars are characterized by their duty factor, D
where is the pulse duration and PRF is the pulse repetition frequency.
For pulsed radars D may range from 1% to 20%.
For CW radars D = 100%.
PRFD
51
FM-CW radarSimple FM-CW block diagram and associated signal waveforms.
FM-CW radar block diagram
52
FM-CW radarLinear FM sweep
Bandwidth: B Repetition period: TR= 1/fm
Round-trip time to target: T = 2R/c
The beat frequency fb = fTx– fRx
The beat signal observation time is TR/2 providing a frequency resolution, f = 2 fm
Therefore the range resolution R = c/2B [m]
]Hz[fc
RB4
Tc
RB4T
2T
Bf m
RRb
53
FM-CW radarThe FM-CW radar has the advantage of constantly illuminating the target (complicating the radar design).
It maps range into frequency and therefore requires additional signal processing to determine target range.
Targets moving relative to the radar will produce a Doppler frequency shift further complicating the processing.
54
Chirp radarBlending the ideas of pulsed radar with linear frequency modulation results in a chirp (or linear FM) radar.
Transmit a long-duration, FM pulse.
Correlate the received signal with a linear FM waveform to produce range dependent target frequencies.
Signal processing (pulse compression) converts frequency into range.
Key parameters:
B, chirp bandwidth
, Tx pulse duration
55
Chirp radar
Linear frequency modulation (chirp) waveform
for 0 t
fC is the starting frequency (Hz)
k is the chirp rate (Hz/s)
C is the starting phase (rad)
B is the chirp bandwidth, B = k
C2
C tk5.0tf2cosA)t(s
56
Receiver signal processingchirp generation and compression
Dispersive delay line is a SAW deviceSAW: surface acoustic wave
57
Stretch chirp processing
58
Challenges with stretch processing
time
TxB Rx
LO
near
farfreq
uen
cy
time
freq
uen
cy near
far
Reference chirp
Received signal (analog)
Digitized signalLow-pass filter
A/D converter
Echoes from targets at various ranges have different start times with constant pulse duration. Makes signal processing more difficult.
To dechirp the signal from extended targets, a local oscillator (LO) chirp with a much greater bandwidth is required. Performing analog dechirp operation relaxes requirement on A/D converter.
59
Pulse compression exampleKey system parametersPt = 10 W, = 100 s, B = 1 GHz, E = 1 mJ , R = 15 cm
Derived system parametersk = 1 GHz / 100 s = 10 MHz / s = 1013 s-2
Echo duration, = 100 sFrequency resolution, f = (observation time)-1 = 10 kHz
Range to first target, R1 = 150 m
T1 = 2 R1 / c = 1 s
Beat frequency, fb = k T1 = 10 MHz
Range to second target, R2 = 150.15 m
T2 = 2 R2 / c = 1.001 s
Beat frequency, fb = k T2 = 10.01 MHz
fb2 – fb1 = 10 kHz which is the resolution of the frequency measurement
60
Pulse compression example (cont.)
With stretch processing a reduced video signal bandwidth is output from the analog portion of the radar receiver.
video bandwidth, Bvid = k Tp where Tp = 2 Wr /c and Wr is the swath’s
slant range width
for Wr = 3 km, Tp = 20 s Bvid = 200 MHz
This relaxes the requirements on the data acquisition system (i.e., analog-to-digital (A/D) converter and associated memory systems).
Without stretch processing the data acquisition system must sample a 1-GHz signal bandwidth requiring a sampling frequency of 2 GHz and memory access times less than 500 ps.
61
Correlation processing of chirp signalsAvoids problems associated with stretch processingInvolves time-domain cross correlation of received signal with
reference signal. {Matlab command: [c,lag] = xcorr(a,b)}
Time-domain cross correlation can be a slow, compute-intensive process.Alternatively we can take advantage of fact that convolution in time domain equivalent to multiplication in frequency domain
Convert received signal to freq domain (FFT)Multiply with freq domain version of reference chirp functionConvert product back to time domain (IFFT)
FFT IFFT
Freq-domain reference chirp
Received signal (after digitization)
Correlated signal
62
Signal correlation examples
Input waveform #1High-SNR gated sinusoid, no delay
Input waveform #2High-SNR gated sinusoid, ~800 count delay
63
Signal correlation examples
Input waveform #1High-SNR gated sinusoid, no delay
Input waveform #2Low-SNR gated sinusoid, ~800 count delay
64
Signal correlation examples
Input waveform #1High-SNR gated chirp, no delay
Input waveform #2High-SNR gated chirp, ~800 count delay
65
Signal correlation examples
Input waveform #1High-SNR gated chirp, no delay
Input waveform #2Low-SNR gated chirp, ~800 count delay
66
Chirp pulse compression and time sidelobes
Peak sidelobe level can be controlled by introducing a weighting function -- however this has side effects.
67
Superposition and multiple targetsSignals from multiple targets do not interfere with one another. (negligible coupling between scatterers)
Free-space propagation, target interaction, radar receiver all have linear transfer functions superposition applies.
Signal from each target adds linearly with signals from other targets.
r is range resolution
68
Why time sidelobes are a problemSidelobes from large-RCS targets with can obscure signals from nearby smaller-RCS targets.
Related to pulse duration, , is the temporal extent of time sidelobes, 2.Time sidelobe amplitude is related to the overall waveform shape.
fb = 2 k R/c
fb
69
Window functions and their effectsTime sidelobes are a side effect of pulse compression.
Windowing the signal prior to frequency analysis helps reduce the effect.
Some common weighting functions and key characteristics
Less common window functions used in radar applications and their key characteristics
70
Window functionsBasic function:
a and b are the –6-dB and - normalized bandwidths
71
Window functions
72
Detailed example of chirp pulse compression
t0,tk5.0tf2cosa)t(s C2
C
C2
CC2
C )Tt(k5.0)Tt(f2cosatk5.0tf2cosa)Tt(s)t(s
CC2
C2
2C
2
2TfTk5.0tktf2tk2cos
)TkTtk2Tf2(cos
2
a)Tt(s)t(s
2C
2
Tk5.0tTkTf2cos2
a)t(q
after lowpass filtering to reject harmonics
dechirp analysis
which simplifies to
received signal
quadraticfrequency
dependence
linearfrequency
dependencephase terms
chirp-squaredterm
sinusoidal term
sinusoidal term
73
Pulse compression effects on SNR and blind range
SNR improvement due to pulse compression is the waveform’s time-bandwidth product: B (regardless of pulse compression scheme used)
Case 1: Pt = 1 MW, = 1 ns, B = 1 GHz, E = 1 mJ, R = 15 cm
For a given R, Gt, Gr, , : SNRvideo = 10 dBB = 1 or 0 dB
SNRcompress = SNRvideo = 10 dBBlind range = c/2 = 0.15 m
Case 2: Pt = 10 W, = 100 s, B = 1 GHz, E = 1 mJ , R = 15 cm
For the same R, Gt, Gr, , : SNRvideo = – 40 dBB = 100,000 or 50 dB
SNRcompress = 10 dBBlind range = c/2 = 15 km
B
FBTkR4
GGPSNR
43
2rtt
compress
(point target range equation)
74
Pulse compressionPulse compression allows us to use a reduced transmitter power and still achieve the desired range resolution.
The costs of applying pulse compression include:
added transmitter and receiver complexity
must contend with time sidelobes
increased blind range
The advantages generally outweigh the disadvantages so pulse compression is used widely.
75
Radar range equation (revisited)
We now integrate the signal-to-noise ratio improvement factors from coherent and incoherent integration as well as pulse compression into the radar range equation for point and distributed targets.
Point targets
Extended targets
FTkR4
NNGGPBNN
FBTkR4
GGPSNR
43inccoh
2rtt
inccoh43
2rtt
FBTkR4sin2
NNcGPBNN
FBTkR4sin2
cGPSNR
033
inccohaz2
t2
inccoh
033
paz2
t2
76
Dynamic range exampleThe SNR improvements discussed (coherent and incoherent integration, pulse compression) also expand the radar’s dynamic range.In modern radars these SNR improvements occur in the digital domain. Consequently the overall dynamic range is not limited by the ADC.
To illustrate this fact consider the following example.A radar uses a Linear Technologies LT2255 ADC
Specs: 14-bit, 125 MS/s, 2-V full scale, 640-MHz analog bandwidth
It samples at 112 MHz (fs) a signal centered at 195 MHz with 30 MHz of bandwidth.At 200 MHz the ADC’s SNR is ~ 70 dB (per the product specifications) indicating an effective number of bits, ENOB = 11.7.2 Vpp 10 dBm in a 50- system
To realize the SNR improvement offered by coherent integration, the thermal noise power must be 3 to 5 dB above the ADC’s quantization noise floor.
77
Dynamic range exampleRadar center frequency is 195 MHz.Radar bandwidth is 30 MHz.Radar spectrum extends from 180 MHz to 210 MHz.
Sampling frequency is 112 MHz.Satisfies the Nyquist-Shannon requirement since fs = 112 MHz > 60 MHzUndersampling is used, therefore analysis is required to ensure signal is centered within a Nyquist zone.
5th Nyquist Zone1st Nyquist Zone 2nd Nyquist Zone 3rd Nyquist Zone 4th Nyquist Zone
2 fS
180 190 200 210 22016090 100 110 120 130 140 1508030 40 50 60 7020100
180 to 210 MHz10 µs
168
222
Frequency (MHz)
fS / 2 fS 3 fS / 2
170
11256
224
0
DC
230 240 250 260 270 280
fs Available center frequencies (MHz) for a 30-MHz signal bandwidth w 40% guardbands
(MHz) 1st Nyquist 2nd Nyquist 3rd Nyquist 4th Nyquist 5th Nyquist 6th Nyquist 7th Nyquist 8th Nyquist 9th Nyquist 10th Nyquist 11th Nyquist 12th Nyquist108 27 81 135 189 243 297 351 405 459 513 567109 27.25 81.75 136.25 190.75 245.25 299.75 354.25 408.75 463.25 517.75 572.25110 27.5 82.5 137.5 192.5 247.5 302.5 357.5 412.5 467.5 522.5 577.5111 27.75 83.25 138.75 194.25 249.75 305.25 360.75 416.25 471.75 527.25 582.75112 28 84 140 196 252 308 364 420 476 532 588113 28.25 84.75 141.25 197.75 254.25 310.75 367.25 423.75 480.25 536.75 593.25114 28.5 85.5 142.5 199.5 256.5 313.5 370.5 427.5 484.5 541.5 598.5115 28.75 86.25 143.75 201.25 258.75 316.25 373.75 431.25 488.75 546.25 603.75116 29 87 145 203 261 319 377 435 493 551 609117 29.25 87.75 146.25 204.75 263.25 321.75 380.25 438.75 497.25 555.75118 29.5 88.5 147.5 206.5 265.5 324.5 383.5 442.5 501.5 560.5119 29.75 89.25 148.75 208.25 267.75 327.25 386.75 446.25 505.75 565.25120 30 90 150 210 270 330 390 450 510 570121 30.25 90.75 151.25 211.75 272.25 332.75 393.25 453.75 514.25 574.75122 30.5 91.5 152.5 213.5 274.5 335.5 396.5 457.5 518.5 579.5123 30.75 92.25 153.75 215.25 276.75 338.25 399.75 461.25 522.75 584.25124 31 93 155 217 279 341 403 465 527 589125 31.25 93.75 156.25 218.75 281.25 343.75 406.25 468.75 531.25 593.75
78
Dynamic range exampleThe radar system has a 10-kHz PRF, a 10-s with 30-MHz bandwidth, and performs 32 presums (coherent integrations) prior to data recording. During post processing pulse compression is applied followed by an additional 128 coherent integrations are performed (following phase corrections or focusing).
These processing steps have the following effects
Signal Noise Dynamicpower power range
ADC 10 dBm -55 dBm 65 dBpresum: Ncoh = 32 30 dB 15 dB 15 dB
pulse compression, B = 300 25 dB 0 dB 25 dBcoherent integration: Ncoh = 128 42 dB 21 dB 21 dB
Overall 107 dBm -19 dBm 126 dB
Thus the radar system has an instantaneous dynamic range of 126 dB despite the fact that the ADC has a 65-dB dynamic range.
LTC
2255
EN
OB
@ 2
00 M
Hz:
11.
7 bi
ts10 dBm(FS: 2 V)
-58 dBm(LSBeff: 400 μV)
A/D convert12 effective bits
65 dB
12
Presum N = 32
80 dB
17
Pulse compressBT = 300
105 dB
21
Coherent integrateNCOH = 128
126 dB
28
Thermal noise, -55 dBm →
FFFH
000H 00000H
1FFFFH
Thermal noise → Thermal noise →
000000H
← Thermal noise
Dynamic range:
Number of bits:
15 dB
21 dB
30 dB
25 dB
42 dB
1FFFFFH
FFFFFFFH
0000000H
126 dB
79
Dynamic range example
Level set by adjusting receiver gain
80
0/ modulationCoherent noise limits the SNR improvement offered by coherent integration.
Using interpulse binary phase modulation (which is removed by the ADC), the SNR improvement range can be improved significantly.
On alternating transmit pulses, the phase of the Tx waveform is shifted by 0 or radians.
Once digitized by the ADC, the phase applied to the Tx waveform is removed (by toggling the sign bit), effectively removing the interpulse phase modulation and permitting presumming to proceed.
This scheme is particularly useful in suppressing coherent signals originating within the radar.
Interpulse phase modulation can also be used to extend the ambiguous range.
+waveform waveform +waveform waveform
81
0/ modulationGraphical illustration of 0/ interpulse phase modulation to suppress coherent interference signals.
+waveform waveform +waveform waveform
+int +int +int +int
+waveform +waveform +waveform +waveform
+int int +int int
Coherent integration produces[+waveform +int] + [+waveform int] + [+waveform +int] + [+waveform int]
= 4 [+waveform]
82
0/ modulationMeasured noise suppression as a function of the number of coherent averages both with and without 0/ interpulse phase modulation.
83
FM-CW radarNow we revisit the FM-CW radar to better understand its advantages and limitations.
CW on continuously (never off) Tx while Rx
Tx signal leaking into Rx limits the dynamic range
OR
84
FM-CW radarCirculator case (in on port 1 out on port 2, in on port 2 out on port 3)
• Leakage through circulator, port 1 port 3isolation maybe as good as 40 dB
• Reflection of Tx signal from antenna back into Rx“good antenna” has S11 < -10 dB
Separate antenna case
• Antenna coupling < - 50 dBisolation enhancements (absorber material, geometry)
Leakage signal must not saturate Rx
85
FM-CW radarFM – frequency modulated
Frequency modulation required to provide range information
Unmodulated CW radarNo range information provided, only DopplerUseful as a motion detector or speed monitorLeakage signal will have no Doppler shift (0 Hz), easy to reject the DC component by placing a high-pass filter after the mixer
FM-CW radar applicationsShort-range sensing or probing
A pulsed system would require a very short pulse duration to avoid the blind range
Altimeter systemsNadir looking, only one large target of interest
FM-CW radar shortcomingsSignals from multiple targets may interact in the mixer producing multiple false targets (if mixing process is not extremely linear)
86
FM-CW radarDesign considerations
Range resolution, R = c/(2 B) [m]Frequency resolution, f = 2/TR [Hz]
Noise power, PN = k T0 B F [W]But the bandwidth is the frequency resolution, f, so
PN = k T0 f F [W]
Example – snow penetrating FM-CW radar
87
FM-CW radarExample – snow penetrating FM-CW radar
B = 2000 – 500 MHz = 1500 MHz R = 10 cm
Frequency resolution, f = 1/sweep time = 1/4 ms = 250 Hz
PN = -140 dBm
Rx gain = 70 dB
PN out = -140 dBm + 70 dB = -70 dBm
ADC saturation power = + 4 dBm
Rx dynamic range, +4 dBm – (-70 dBm) = 74 dBConsistent with the ADC’s 72-dB dynamic range
FM slope (like the chirp rate, k), 1500 MHz/4 ms = 375 MHz/ms
So for target #1 at 17-m range, t = 2R1/c = 113 ns
Beat frequency, fb = 113 ns 375 MHz/ms = 42.5 kHz
fb - f = 42.25 kHz range to target #2, R2 = 16.9 m R = 10 cm
Note: 1500-MHz bandwidth, 42-kHz beat frequency
88
FM-CW radar block diagram
HPFLPF
89
FM-CW radar – RF circuitry9” x 6.5” x 1” module
90
Measured radar data
Measured radar data from Summit, Greenland in July 2005
Laboratory test data
91
Bistatic / multistatic radarBistatic radar
one transmitter, one receiver, separated by baseline L, and
bistatic angle, , is greater than either antenna’s beamwidth
OR
L/RT or L/RR > ~20%
The three points (Tx, Rx, target)comprising the bistatic geometryform the bistatic triangle that lies inthe bistatic plane.
Multistatic radarmore than one transmitter or receiver separated
bistaticangle
Txantenna
Rxantenna
Lbaseline
RT
RR
target
92
Bistatic / multistatic radarWhy use a bistatic or multistatic configuration?
Covert operation• no Tx signal to give away position or activity
Exploit bistatic scattering characteristics• forward scatter » backscatter
Passive radar or “hitchhiker”• exploit transmitters of opportunity to save cost• example transmitters include other radars, TV, radio, comm satellites, GPS,
lightning, the Sun
Counter ARM (ARM = anti-radiation missile)• missile that targets transmit antennas by homing in on the source
Counter retrodirective jammers• high-gain jamming antenna directing jamming signal toward the transmitter location
Counter stealth• some stealth techniques optimized to reduce backscatter, not forward scatter
Homing missile• transmitter on missile launcher, receiver on missile (simplifies missile system)
Unique spatial coverage• received signal originates from intersection of Tx and Rx antenna beams
93
Bistatic radar geometryFor a monostatic radar the range shell representing points at equal range (isorange) at an instant forms a sphere centered on the radar’s antenna.For a bistatic radar the isorange surface forms an ellipse with the Tx and Rx antennas at the foci.That is, RT + RR = constant everywhere on the ellipse’s surface.
Consequently, echoes from targets that lie on the ellipse have the same time-of-arrival and cannot be resolved based on range.
94
Bistatic range resolutionThe bistatic range resolution depends on the target’s position relative to the bistatic triangle.
For targets on the bistatic bisector the range resolution is RB
For targets not on the bisectorthe range resolution is R
Therefore for target pairs on the ellipse, = 90 and
R , i.e., negligible range resolution.
Note: For the monostatic case, = 0 and R = c/2.
2cos2
cR B
cos2cos2
cR
R
RB
/2
Rx
RT
RR
target
Tx
/2
bistatic
bisector
95
Bistatic DopplerThe Doppler frequency shift due to relative motion in the bistatic radar geometry is found using
For the case where both the transmitter and receiver are stationarywhile the target is moving, the Doppler frequency shift is
Note: For the monostatic case, = 0 and fd = 2 VTGT cos ()/
td
Rd
td
Rd1RR
td
d1f RT
RTB
2coscosV2
f TGTB
Rx
TGT
TxVTGT
VRX
VTX
RT
RR
/2
Rx
RT
RR
Tx
bistatic
bisector
VTGT
TGT
VTX = 0
VRX = 0
96
Bistatic DopplerFor the case where both the transmitter and receiver are moving while the target is stationary, the Doppler frequency shift is
Another way to determine the Doppler shift for the general case where the transmitter, receiver, and target are moving is to numerically compute the ranges (RT and RR) to the target position as a function of time. Use numerical differentiation
to find dRT/dt and dRR/dt that can then be used in
This approach can also be used to produce isodops (contours of constant Doppler shift) on a surface by numerically computing fB to each point on the surface.
Matlab’s contour command is particularly useful here.
RRRX
TTTX
B cosv
cosv
f
Rx
TGT
Tx
VTGT = 0
VRX
VTX
RT
RR
R
R
T
T
td
Rd
td
Rd1f RT
B
97
Example plotsMonostatic exampleAircraft flying straight and levelx = 0, y = 0, z = 2000 m
vx = 0, vy = 100 m/s, vz = 0
f = 200 MHz
98
Example plotsBistatic exampleTx (stationary atop mountain):x = -6 km, y = -6 km, z = 500 mvx = 0, vy = 0, vz = 0
Rx (aircraft flying straight and level):x = 0, y = 0, z = 2 kmvx = 0, vy = 100 m/s, vz = 0
f = 200 MHz
99