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EET 323
1
Fig. 1. Operational amplifier
Abstract—Operational amplifiers (Op-Amp) are used in linear
AC operations and are widely used in electronic industry. What
follows are two operational amplifier designs using bipolar
junction Transistor (BJT) Technology and metal oxide
semiconductor field effect transistor (MOSFET) Technology.
These designs will focus in the input stage and gain stages. The
BJT will be modeled as an Op-Amp and characterized.
Index Terms—Operational amplifiers, Power electronics.
I. INTRODUCTION
N operational amplifier is made up of several transistors.
The Bipolar Junction Transistor (BJT) is widely used with
different configurations, and different transistors for different
models of op-amps. The op-amp has an inverting input and a
non-inverting input with one output as in Fig. 1. The op-amp
is powered by ±VDC.
Section II will have a BJT Design, Section III will show the
results of the simulation of the BJT design, Section IV will
have a MOSFET design, and Section V will conclude with a
few notes.
II. BJT OP-AMP DESIGN
I designed a three stage operation amplifier with BJT using a
cascode current mirror to bias the input stage and the gain
stage. I added two emitter followers on the inputs to increase
input impedance. I also added emitter followers on the gain
stage to match impedances from the input stage. I used four
different transistors for this design.
NTE912 SSM2210
β1 = 100 β3 = 605
VA = 100V VA = 40V
SSM2210 2N3906
β3 = 165 β4 = 300
VA = 40V VA = 100V
Manuscript received March 20, 2008. This work was supported in part by
Oregon Institute of Technology.
D. L. Longstreet is with the Oregon Institute of Technology, Portland, OR
97006 USA (corresponding author to provide phone: 503-866-5561; e-mail:
I designed the cascode current mirror for a current of 2mA
using the SSM2210 transistor arrays to bias the input stage and
the gain stage.
VCC and VEE = ±20V.
RC1 = RC2 = 10kΩ
IC = 1mA
re' = 26Ω
mAk
vvIc 14.2
18
4.140=
Ω−
=
The gain of the input stage is
192 2
101
'
=Ω
=er
kAv
Input impedance is
Ω=
Ω××=
××=
0k26
26100100
'
Zin
Zin
reZin ββ
The common mode gain is
000413.0
605*20226
10
2'
−=Ω×+Ω
Ω−=
+−
=
k
k
RTre
RcACM
Operational Amplifier design with BJT
& MOSFET Technology
Daniel L. Longstreet
A
EET 323
2
The common mode rejection ratio is
dBCMRR
ACM
AvLogCMRR
113
120
=
=
The gain stage consists of a differential pair with an active
load. The differential stage is biased with the cascode current
mirror.
The gain of this stage is the output resistance of the active load
divided by 2(Re+re'). Also I ran into the problem of reduce
voltage swing as the voltage at the emitters of the differential
amplifiers was not close to zero but was around 8.3V. I
centered my voltage around 14V for a max swing of ±6V.
Ω== kmA
VRo 40
1
40
770262
402 =
Ω×Ω
=k
Av
The output stage was design for low output impedance. I used
a common emitter to drop the voltage from 14V to around
1.4V and then used a Darlington pair to reduce my output
impedance. The DC out put component was 0.5V. This could
be adjusted by changing the amount of voltage drop across the
common emitter amplifier in the previous stage.
Ignoring loading effect (as I believe that I can as I designed
each stage accordingly) the over all calculated gain was about
150,000.
III. BJT OP-AMP SIMULATIONS
After the design process was finished I build and tested my
design. I had problems getting the cascode current mirrors to
function correctly so a removed them and replace them with a
basic current mirror. This did reduce my CMRR but I was still
satisfied with the results. I look at the open loop gain,
measured the common mode gain and measured the input
impedance. I tested my design with a negative feedback
network with a gain of -10 and a non-inverting gain of 1. The
results can be seen if fig. XX in the appendix.
TABLE I – Characteristic of the BJT OP-Amp
Parameter Condition Dan's
OPAMP
Units
Input Offset
Voltage
TA = 25°C 111 mV
Input Offset
Current
TA = 25°C 200 µA
Input Bias
Current
TA = 25°C 9.1 µA
Input
Resistance
TA = 25°C 400 kΩ
Output
Voltage Swing
VS = ±15V
RL ≥ 1kΩ
± 5 V
Output Short
Circuit Current
TA = 25°C 45 mA
CMRR TA = 25°C
f = 1 kHz
60 dB
Bandwidth TA = 25°C 2 MHz
Slew Rate 0.2 V/µs
.
IV. MOSFET DESIGN
I was not as happy with the MOSFET OP-Amp Design as I had
so difficulties with centering my voltage from the differential
gain stage. Besides that everything was straight forward. I
designed a cascode current mirror for a current of 2mA. This
bias the differential pair and the active loads. I used the
CD4007 transistor array to model my design.
N-Channel
KP = 111µ
Vto = 2v
P-Channel
KP = 55µ
Vto = -1.5V
( )( )vVgs
vVgsmA
VtoVgskId
24.6
211122
2
=
−=
−=
µ
Implementing a cascode current mirror the bias resistor is
Ω=
−=
kR
mAR
bias
bias
76.13
2
24.6*240
I modeled my design in LTSpice and got a simulated open loop
gain of around 10,000. Also I connect a negative feed back
network to control the gain with a gain of -10. as seen in Fig. 2.
You can see in Fig. 3 that this design does not allow for more
then 1.2Vp swing.
EET 323
3
Fig. 2. MOSFET inverting amplifier Av = -10
Fig. 3. MOSFET inverting amplifier Av = -10
V. CONCLUSION
There are a few things that I should have done differently in
the BJT design. I could have added emitter resistors to
increase the input impedance or I could have used the
SSM2210 with a Beta of 605 at 1mA. That would have
increased Zin to 9.5MΩ. I should have picked transistors with
a higher early voltage to get more gain when used as an active
load and better CMRR when used as a current mirror. I still
need no learn more about voltage shifters and output stages to
improve the BJT design.
I was not very satisfied with my MOSFET design but I do
understand the current mirror and active loads.
EET 323
4
APPENDIX
Fig. 4. BJT OP-Amp Design
Fig. 5. MOSFET OP-Amp design
EET 323
5
Fig. 6. BJT OP-Amp Open loop gain
Fig. 7. BJT OP-Amp with negative feedback Av = -10
Fig. 8. BJT OP-Amp Non-inverting Av = 1
Fig. 9. BJT OP-Amp Measuring Slew Rate. SR = 0.2 v/µs
Fig. 10. BJT OP-Amp Measuring Common mode gain ACM = 0.001
Daniel L. Longstreet is pursuing his Bachelor of Science in Electronic
Engineering Technology from the Oregon Institute of Technology in Portland,
OR USA and is expected to graduate June 2009. He also has an Associates of
Science in Industrial Electronics from the Technical College of the
LowCounrty Beaufort, SC. USA May 2005.
He is working at TriQuint Semiconductor in Hillsboro Oregon as a RF Test
Technician.