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Introduction to Sigma Delta Converters
P.V. Ananda Mohan
Electronics Corporation of India Limited,
Bangalore
How to reduce analog part?
• Use Sigma-Delta Conversion• Front-end simple active RC Filter
• SC/Gm-C Sigma- Delta converter working at high sampling frequency
• Digital Decimation Filter using DSP• Scalable with digital technology• Only few OTAs or opamps, one comparator
needed, MOS switches needed
MODERN CODEC-FILTER
Active RC Filter
input
SIGMA-DELTA Converter
Decimation Digital Filter Digital
outputOver sampling
Clock Digital Filter clocks
What is sigma-delta conversion?
• Similar to Delta Modulation but can code dc (i.e.Slowly varying signals)
• Generates One bit output sequence • Output word is obtained from this sequence by finding
the average using a decimator.• Also called “Pulse density modulation”• Also called “over-sampled A/D conversion”• High resolution up to 19 bits• Uses Oversampling and Noise shaping• Trades off accuracy in amplitude with accuracy in time
Advantages
• Analog part small area
• Over sampling ratio typically 8 to 256.
• Megahertz range up to 16 bits
• Band-pass Sigma –delta solutions are also available.
First-Order Sigma Delta Modulator
+
-
+
-
I bit DAC
Integrator
Comparator
Difference amplifier
V1Vin
Vref
V2 Consider Vin=0.2 volts and Vref=1 volt.Number V1 V2 V0 Dout
1 .2 .2 1 1 2 -.8 - .6 0 - 1 3 1.2 .6 1 1 4 - .8 - .2 0 - 1 5 1.2 1.0 1 1 6 -.8 .2 1 1 7 - .8 -.6 0 -1 8 1.2 .6 1 1 9 -.8 - .2 0 -1Average of Dout = (-1+1-1+1+1)/5 = 1/5 = 0.2 Result for 20 samples Input volts Sequence of output bits0.0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 10.1 1 0 1 0 1 0 1 0 1 0 1 1 0 1 0 1 0 1 0 10.2 1 0 1 0 1 1 0 1 0 1 1 0 1 0 1 1 0 1 0 10.7 1 1 1 0 1 1 1 1 1 0 1 1 1 1 1 1 0 1 1 10.9 1 1 1 1 1 1 1 1 1 0 1 1 1 1 1 1 1 1 1 11.0 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1 1
•Vo(z)= Vi(z)+en.(1-z-1)
Vo
Two-loop Sigma-delta modulator
• Vo(z)=Vi(z)+en.(1-z-1)2 Second order noise shaping
+ Integratorz-1/(1-z-1)
+ Integratorz-1/(1-z-1)
comparator
latch
input
+
output
clock
2
Latch
Quantization noise of a linear A/D
• Difference between staircase and linear is a triangular waveform.
/2
-/2
input
output
Linear models for Analysis
• Vo(z)= Vi(z)+en.(1-z-1)
• Input low-pass and en high-pass transfer function; Shaping the Quantization noise!!!
+
-
+
-
I bit DAC
Integrator
Comparator
Difference amplifier
V1Ain
Vref
V2
en
Integratorz-1/(1-z-1)Vi Vout
-
z-1
Integrator or Accumulator
Quantization noise for an A/D converter
12..
12
2/
2/
22
eee qqnd
If peak to peak is FSR (Full scale range) , RMS value is FSR /(22).
02.6
76.1
)76.102.6(02.678.702.62
6log.20
2
6
22
12
12
22
12
2
22
2
SNRENOB
dBNN
FSR
FSR
SNR
N
dB
NN
N
RMS
SNR
V
Quantization noise of a Sigma delta converter
• Noise shaping function (1-z-1) L
• (1-z-1) L = (1-e-jωT) L = (e-jωT/2)L.(ejωT/2 -e-jωT/2)L
• |(1-z-1) L | = | (ejωT/2 -e-jωT/2)L | = 2. Sin(πf/fs)
• = (2 πf/fs)L
12.
12.
12.
12.
1211
22
1212
2
2
2
22
2
1
Ls
Ls
dfNoise
LL
L
L
L
Tejz
L
s
f
fff
zf
Candy’s Formula
M
f
f
L
LL
L
L
Ls
DRRangeDynamic12
222
12
2
.12
.2
3
12.
12.
22
02.6
76.1DRdB
ENOB
Advantages
• (1-z-1)L has L zeros at dc
• Signal and Quantization noise are treated differently.
• Output word is obtained from a sequence of coarsely sampled input samples.
• Analog part small area
• Typical oversampling ratio 8 to 256.
• For a Nyquist rate ADC DR2 = 3.22B-1
• For Second Order Sigma delta Converter,
16.5
.2
3 54
DR
16.7
.2
3 76
DRM16, L=3
M=16, L=2
Ratio is 15.6 dB.
For M = 256, Ratio is ?????
Decimation filter
• Occupies large area and consumes power.• Linear Phase FIR filter can be used.• Comb filters preferred since the input data
is one bit wide only.• Can Reduce sampling rate to four times the
Nyquist rate.• Lth order Noise shaping function, L+1th
order decimator is required.
Decimation filter
• Local average can be computed efficiently by by a decimator.
• Frequency response
)sin(
)sin(.
111
1
T sfT sfD
Dz
z Dk k
Decimation filter
• Decimation is reduction of sampling rate• Comb filters are used• Fixed coefficient FIR filters• One,Two or Three stages• Some designs use fixed coefficient IIR filters• Second order Sigma delta converter neds third-
order decimator filter.
Decimation filter example
input
output
clockAccumulator
Latch
Input Stream
Output word
Lower Clock
• H(z) = (1-z-64)/(1-z-1)
DECIMATION FILTERS
• Second order Decimator • H(z) = (1-z-64)2/(1-z-1)2
• Third-Order Decimator• H(z) = (1-z-64)3/(1-z-1)3
• Design is slightly involved-Three parallel processors
• Coefficient generation is dynamic for both designs
ARCHITECTURES
ARCHITECTURES
• Single stage Multiloop feedback
• Multistage Noise Shaping (MASH)
• Cascade Designs
• Leslie-Singh Architecture
Fifth order single stage delta sigma modulator
+ ++
+
z-1/(1-z-1)
z-1/(1-z-1)
z-1/(1-z-1)
z-1/(1-z-1)
Q
z-1/(1-z-1)
in
a1 a3 a4 a5a2
+- - - -
-
Q Quantizer n bit Output
Fifth-Order Leap-Frog Sigma-Delta Modulator
-
-
B2 b4 b5
a1 a2 a3 a4 a5
z-1/(1-z-1)
z-1/(1-z-1)
z-1/(1-z-1)
z-1/(1-z-1)
z-1/(1-z-1)
ADC
DAC
OUT
b1 b3 b5
-
--
-
IN
Single Loop Designs• No non linearity of DAC problems: only two
levels one and zero.• Quantization noise power is very high and hence
Need large over-sampling ratio• Single loop Sigma-delta modulators, gain
progressively increases and overloads the comparator.
• Delay also. Input change is felt after five stages.• High coefficient spread (large area)
Single Loop Designs
• High coefficient sensitivity
• Poor stability
• All known digital filter structures cascade, direct form, Leap frog can be used.
• Single loop Sigma delta modulators reduce integrator gin to achieve stability.
Multi stage noise shaping (MASH) Architecture
-
-
-
-
C1
X(z)
1/(1-z-1)
z-1
Cpmparator
-
1/(1-z-1)
z-1
Cpmparator
-
1/(1-z-1)
z-1
Cpmparator
-
-
z-1
C3
C2
z-1z-1
MASH
• Leakage is proportional to 1/Av2
• Leakage is proportional to σC2
MASH• Only last stage noise ideally remains.• Noise, distortion performance and Power dissipation
dependent largely on the first stage leakage.• Digital Noise cancellation circuits.• Output is a word not a bit as in the case of Single stage
1 bit A/D based design.• Complicates digital filters following the Analog blocks.• Linear single bit Quantizer in the first stage• MASH needs to have low leakage, high opamp gain
90dB low voltage applications not easily realizable.
MASH
• Leakage of Quantization noise from each stage is because of the finite gain of the OA
• Capacitor mismatch also leads to leakage.
• Many versions available called as 1-1-1,1-2-1, etc indicating the order of the loop in each stage.
• Upto fifth order modulators built.
Leslie-Singh Architecture
L(z) N-bitADC
1/L(z)
1-bitDAC
N N
1
N+1
+
-
L(z) 1-bitADC
H1(z)
1-bitDAC
N N
1
N+1
+
-
N-bitADC
H2(z)
Leslie-Singh Architecture
• This Architecture avoids matching problems of DAC in first stage. Uses Two ADCs in effect.
1-bitADC
2z-1-z-2
1-bitDAC
N N-N+1
+-
N-bitADC
(1-z-1)2
Z-1 Z-1
Why Multi-bit Sigma delta converters?
• SNR can be improved by using multi-bit without clocking fast, Candy’s formula
• Problem of mismatch of resistors/capacitors occurs• Nonlinearity of DAC is troublesome• Number of bits increases exponentially the
complexity (number of capacitors/resistors)• Typically restricted to 4 or 5 bits.• Can be used as single stage Multibit or one stage of
MASH
Bandpass Sigma Delta
• Advantage immune to 1/f noise
• No need for matching I and Q signals
Resonator
-
Input
Band-Pass Sigma delta Modulator
• H(z)=z-2 and N(z)=(1+z-2)2 Transmission zeroes at fs/4, Obtained by z-1 to –z-2 transformation.
z-1/(1+z-2)
z-1/(1+z-2)
Comparator
z-1 z-1
1-1
1/2
X(z)
Y(z)
IMPLEMENTATION OPTIONS
Implementation Options
• Switched Capacitor
• OTA-C
• Continuous-time
• Combinations
SC Filters
SC solution
• SC preferred because of accurate control of integrator gains.
• Fully Differential design increases signal swing by two and dynamic range by 6dB.
• Common mode signals such as supply lines, substrate are rejected
• Charges injected by switches are cancelled.
• First integrator is important regarding noise, linearity, settling behavior since second stage
• Folded cascode Opamps recommended.• Nonidealities of comparator undergo noise
shaping and hence not very critical.• Comparator can be simple.• Capacitors chosen based on noise requirements.
Stray-Insensitive Inverting Integrator
Vi
C1
C2
Vo
1
2
1
2
Stray-Insensitive Non-inverting Integrator
Vo
1
2
Vi
C1
C21
2
Typical Fully Differential SC integrator
CCΦ1d
Φ2
_
+
Y YBΦ1
Φ2
Φ1Y
YB
Φ1d
VREF+ VREF-
VREF- VREF+
Y
YB
2C
2C
Timing to avoid charge injection
Ф1
Ф2
Ф1d
Ф2d
Switch Implementation
• Low ON resistance
• Clock Feed-through (reduced by NMOS transistor shunted by PMOS transistor)
• Effect is to cause dc offset due to aliasing!
S
G
D
Inverter
Auto Zero-ed Integrator
• Haug-Maloberti-Temes
• Cancels noise, offset and finite gain effects
• Output held over a clock period.
-
+
C2
C4
C3
C1
o
e
o
e
o
e
o
e
o
ViVo
Switch Non-idealities• Fully-differential circuits recommended• Duplicated hardware; more area• Noise of switch due to ON resistance• kT/C noise, large capacitors need to be used for low
noise, noise independent of Switch ON resistance Ron
• Charging and discharging time dependent on• SC Sigma delta modulators OA of large bandwidth
at least five times the sampling frequency and high gain are required.
COMPARATORS
• Similar to OPAMPS but need logic level outputs
• Input referred offset of MOS Opamps/comparators is quite high.
• Offset compensation mandatory.• 10 bit ADC with 1V signal, accuracy of a
comparator is 1mV. Thus, residual offset has to be much smaller than 1mV.
A MOS comparator Combining gain stage and latch
Out+
M7M6
M5
M4
M3
M1 M2
In-
VB2
M9
M8
Out-
In+
VB1
StrobeStrobe bar
Typical Bipolar Comparator
• Latch is a regenerative (positive feedback ) circuit
Input
Vout
CKCKINV
Latch
Preamplifier
Flash Architectures for Multibit Sigma delta converters
• Quite fast
• Number of comparators needed exponentially increases with bit length.
• Resistor ladders needed.
• Usually 4 to 5 bit Flash A/D used to reduce area.
Flash architecture
Comparators
inputVref
Th
erm
ome
ter
cod
e
Polysilicon
Resistor Ladder
Flash D/A converter Imperfections
• Integral non-linearity
• Differential non-linearity
• Ac bowing due to input bias current drawn by comparators.
• Comparator kickback noise during transit from latching to tracking
CT Sigma Delta Modulators
CT loop filter
ADC
DAC
_Input
CT Sigma Delta Modulators• Help to increase the clock frequency• Consume less power • OSR needs to be reduced for high bandwidth
applications.• No settling behavior problems.• Relaxed sampling networks• More sensitive to clock jitter• ADC jitter not much trouble• But DAC jitter troublesome. Since it is not noise shaped • Non-zero excess loop delay
CT Sigma Delta Modulators
• Large RC time constant variation• Mismatch between analog noise shaping and
digital noise shaping• CT Filters several alternative technologies
abvailable:• Active RC linear, not tunable• Gm-C less power consumption,High frequency,
tunable • MOSFET-C non-linearity, advantage of tunability
• First stage is very important
• Mixture of Active RC ,Gm-C used.
• First stage Active RC for good linearity
• Compensation capacitors not needed for Gm-C since integrator capacitor can compensate the OTA
Sigma delta DAC
• More tolerant to component mismatch and circuit non-idealities
• More digital
• Keeping circuit noise low, and meeting linearity are the challenges.
Sigma Delta DAC
Digital Input
Interpolation
Digital Code Conversion
0= 100000 =-11= 011111=+1
Digital fiter
MSB
-VREF
-VREF
AnalogLow-pass filter
VREF
DAC
fN fS
fS =M.fN
fS
fS
AnalogOutput
How to combat Nonlinearity of DAC?
• Capacitors/Resistors do have mismatch. Randomize the mismatch.
• In DWA, same set of DAC elements are used cyclically and repeatedly under the guide of a single pointer.
• The element mismatch errors translate to tones at the DAC output when the DAC input has a periodic pattern.
• DEM Logic must be optimized for low delay.
DEM Flash output Thermometer code
0 0 0 0 0 0 0 0 0 0 0 1 1 1 1 1 =5
0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 1 =9
0 0 0 0 0 0 0 0 0 0 0 0 0 1 1 1 =3
0 0 0 0 1 1 1 1 1 1 1 1 1 1 1 1 =12
-
+
C
C
C
C
Sixteen capacitors
1
2
15
16
x x x x X
x x x x x x x x x
x x x
x x x x x x x x x x x x
Power Dissipation
• Settling performance of the Opamp decides gm.
• Power dissipation is dependent on bias current which is decided by Gm.
General Guidelines• Stability (Overload)• Long strings of ones or zeroes are detected and reset is given to
integrators to improve stability.• Stabilization techniques needed e.g. clamping of integrator
outputs.• Extensive simulation needed e.g Matlab Sigma Delta Tool Box
R.Schrier • Rules of Thumb• Maximum of Magnitude of H(z) shall be <1.5 (Lee’s rule)• More relaxed designs available now: Magnitude of H(z) up to 6. • Idle tones in band
General Guidelines• Thumb rule GB of OA > 2.5FS
• Switch resistances can be as low as 150 Ohms.• Offset of Comparator <10mV• Hysteresis of comparator <20mV • Single stage modulators are quite tolerant of nonidealities• Instability means that large not necessarily unbounded
states gives poor SNR compared to linear models.• Reducing OBG (Out of band gain) improves stability• Capacitors with low voltage coefficients ensure good
linearity.
General Guidelines
• OPamps with large dc gain in first stage.• Cancellation of even harmonics feasible by
fully differential circuits• Top plates of capacitors to virtual grounds
of Opamps• Full switches parallel NMOS and PMOS for
input whereas only NMOS for those feeding virtual ground.
General Guidelines
• Comparator metastability• Effect of clock jitter is independent of the
order or structure of the modulator.• Clock A cos(ωot) becomes due to jitter A
cos(ωo(t+αSin(ωt)).This adds to the input and sidebands are formed: ωo+ ω, and ωo- ω) of amplitude A α ωo/2
• SNR is affected by A2 ωo2/2
Sigma Delta Frequency Synthesizer
Frequency reference
Multimodulus frequency divider
VCOLoop FilterPhase Detector
Sigma-Delta ModulatorPrecompensation
FilterGaussian Filter
Data Sequence
Conclusion
• More than 400 papers• IEEE press books• Simulation tools• Months of simulation may be needed to
weed out problems.• Several solutions• Applications emerging for 802.11, Blue
Tooth, CDMA/GSM/3G handsets
Thank You
