Upload
dale-mosley
View
215
Download
1
Tags:
Embed Size (px)
Citation preview
Integrated Circuits Laboratory
Faculty of Engineering
28-January-2003
Decimation FilterDecimation FilterA Design PerspectiveA Design Perspective
Presented by: Sameh Assem Ibrahim
2/36 Integrated Circuits Laboratory
Faculty of Engineering
What is Decimation ?What is Decimation ?
Two types of sampling rate conversion
- Interpolation when F’ > F or T’ < T (inserting L-1 equidistant zero-valued samples between two consecutive samples of x[n] )
- Decimation when F’ < F or T’ > T (keeping every M-th sample of x[n] and removing M-1 in-between samples to generate y[m])
Decimation factor M
M = F’/F <1
A block diagram representation
Mx[n] y[m]
3/36 Integrated Circuits Laboratory
Faculty of Engineering
The Use of Decimation in ΣΔ ADCThe Use of Decimation in ΣΔ ADC
ΣΔ loopsAnalog
inputDecimator
Digital
FS
Analog
Output FN
FS is the high sampling rate used in the ΣΔ modulator
FN is the Nyquist Sampling Rate = 2 Fmax
FS >> FN
FS/FN = M
-1--1-
1 bit Multiple bits
4/36 Integrated Circuits Laboratory
Faculty of Engineering
The Use of Decimation in ΣΔ ADCThe Use of Decimation in ΣΔ ADC
Converts ΣΔ bits stream into PCM data of required resolution (16 bits in our case)
Reduces the sampling rate to Nyquist rate. This helps in:
* Preventing inefficient use of bandwidth
* Reduced speed of operation in the following circuits
Suppresses out of band noise
-2--2-
5/36 Integrated Circuits Laboratory
Faculty of Engineering
Can we just Decrease the Sampling Can we just Decrease the Sampling Rate? Rate?
ω
X(j ω)
-2πFmax 0 2πFmax 2πFS4πFS
FS > 2 Fmax
ω
X(j ω)
-2πFmax 0 2πFmax
2πFS 4πFS
FS < 2 Fmax
6πFS 8πFS 10πFS12πFS
Aliasing
-1--1-
6/36 Integrated Circuits Laboratory
Faculty of Engineering
Can we just Decrease the Sampling Can we just Decrease the Sampling Rate? Rate?
ω
X(j ω)
0
-2--2-
2πFS4πFS
ΣΔ (FS >> 2 Fmax)
2πFN
4πFN
6πFN
No Problem if FS is integer multiples of
FN
Really??
ω
X(j ω)
0 2πFS4πFS
ΣΔ (FS >> 2 Fmax)
πFS
Noise shaped by ΣΔ
2πFNProblem
7/36 Integrated Circuits Laboratory
Faculty of Engineering
Can we just Decrease the Sampling Can we just Decrease the Sampling Rate?Rate?
A decimation filter is needed
Design of a decimator is the design of its decimation filter
Decimation filter is a digital filter
It must have zeros at the integer multiples of the new sampling rate
The Block diagram including the filter
--33--
Mx[n] y[m]h[n]y[n]
8/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundThe Z-transformThe Z-transform
Z-transform is the discrete time counterpart of the Laplace transform
Used in the analysis of LTI systems
Used in the study of stability of a filter
n
nz]n[x)z(X
)z(X)z(H)z(Y
k
]k[h
Unit circle
Re{z}
Im{z}
9/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundSome Z-transform PropertiesSome Z-transform Properties
Linearity
Time shifting
Scaling in the z-domain
Time expansion
Convolution
First difference
Accumulation
)z(bX)z(aX]n[bx]n[ax 2121
)z(Xz]nn[x ono
)ze(X]n[xe oo ωjnωj
)z
z(X]n[xz
o
no
)z(Xrkn,0
rkn],r[x]n[x k
)k(
)z(X)z(X]n[x*]n[x 2121
)z(X)z1(]1n[x]n[x 1
)z(Xz1
1]k[x
1k
10/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundThe Discrete Fourier TransformThe Discrete Fourier Transform
Discrete Fourier transform is the discrete time counterpart of the continuous time Fourier transform
In z-domain:
Put r=1:
Used in estimating the frequency response of a filter
ωjrez
n
nωjωj e]n[x)e(X]}n[x{F
ωde)e(Xπ2
1)}e(X{F]n[x nωj
π2
ωjωj1
11/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundSignal Flow Graphs Basic ElementsSignal Flow Graphs Basic Elements
Operation SymbolTime domain Description
Frequency domain Description
Unit delay x[n] z-1 y[n] y[n]=x[n-1]
M-sample delay x[n] z-M y[n] y[n]=x[n-M]
Gain x[n] c y[n] y[n]=cx[n]
Gain and delay x[n] cz-1 y[n] y[n]=cx[n-1]
Sampling rate compressor
x[n] y[m]y[m]=x[Mm]
Sampling rate expander
x[n] y[m]
Input branch x[n] -- --
Output branch y[n] -- --
M
L
)e(Xe)e(Y ωjωjωj
)e(Xe)e(Y ωjωjMωj
)e(cX)e(Y ωjωj
)e(Xce)e(Y ωjωjωj
otherwise0
,..L2,L,0m]L/m[x]m[y )e(X)e(Y Lωjωj
1M
0l
M/)lπ2ω(jωj )e(XM
1)e(Y
12/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundSignal Flow Graphs OperationsSignal Flow Graphs Operations
x1[n]
x2[n] y[n]=x1[n]+x2[n]+x3[n]
y3[n]=x[n]
x3[n]
x[n]y1[n]=x[n]
y2[n]=x[n]
z-1
c1 c2
x[n] y[n]
y[n]=x[n]+c2x[n-1]+c1y[n-1]
13/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundBasic Elements ImplementationsBasic Elements Implementations
Delay units are implemented as D-FFs
Gain units are implemented as digital multipliers implemented in VHDL or through ALUs
Coefficients to be multiplied with are either stored in a ROM or have a generating digital circuitry if they have an easily implemented function
Adding branches can be done using VHDL adders or ALUs
Accumulators and first difference
14/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundSignal Flow CommutationSignal Flow Commutation
Two branch operations commute if the order of their cascade operation can be interchanged without affecting the input-to-output response of the cascaded system.
15/36 Integrated Circuits Laboratory
Faculty of Engineering
Digital Filters BackgroundDigital Filters BackgroundFIR vs. IIR FiltersFIR vs. IIR FiltersFIR IIR
The impulse response is non-zero for N samples only
The impulse response duration is infinite
They don’t contain any poles in the z-domain
Have both poles and zeros in the z-domain
Have no continuous time counterpart
Are easily derived from continuous time filters
Linear phase can be easily achieved
Linear phase can only be approximated
Always stable Must be checked for stability
Coefficients can be rounded to reasonable word lengths
This will result in large quantization noise
Higher order than IIR is always required
IIR filters are generally very efficient
Most Implemented ΣΔ ADCs use FIR implementation
16/36 Integrated Circuits Laboratory
Faculty of Engineering
Decimation Filter RealizationDecimation Filter Realization
Structures used can be classified into:
1. Direct Form Structures
2. Polyphase structures
3. Structures with time varying coefficients
Each of these can be implemented using FIR or IIR filters.
The choice depends on the application used
Structures 3 are particularly useful when considering conversion by factors of L/M (not our case)
Structures 1 and 2 can both be used
17/36 Integrated Circuits Laboratory
Faculty of Engineering
FIR Direct Form StructuresFIR Direct Form Structures
A direct implementation of the convolution equation
In many applications the FIR filter is designed to have linear phase
Consequently, the impulse response is symmetric
1
0
][][][N
k
knxkhny
]1[][ kNhkh
18/36 Integrated Circuits Laboratory
Faculty of Engineering
FIR Direct Form Structures for FIR Direct Form Structures for DecimatorsDecimators
Multiplications and additions are done at the low sampling frequency
1
0
][][][N
n
nMmxnhmy
19/36 Integrated Circuits Laboratory
Faculty of Engineering
Polyphase FIR Structures for Polyphase FIR Structures for DecimatorsDecimators
Savings of a factor of M in the storage requirements can be achieved by proper design of filters
20/36 Integrated Circuits Laboratory
Faculty of Engineering
Single Stage vs. Multiple Stages Single Stage vs. Multiple Stages
If M can be factored into the product
Then Decimation can be done in stages
I
iiMM
1
M1x[n] y[m]h[n] M2
FSFS FS/M1
FS/M1M2=FS/M
No Advantage
21/36 Integrated Circuits Laboratory
Faculty of Engineering
Filter Design ProcedureFilter Design Procedure
Most implemented ΣΔ ADCs use a two stages decimation filter
1st Stage
A Comb (sinck) Filter
2nd Stage
An FIR filter with symmetric
coefficients
The first stage is realized as a direct form structure
Reduces the sampling rate to 1/16 FS
Introduces zeros around multiples of the new sampling frequencies
These frequencies would alias into the required band and thus increases noise
The 2nd stage reduces sampling rate to the Nyquist frequency
Provides the sharp filtering necessary to reduce the frequency aliasing effect
Provides the passband response compensation for the droop introduced by the “comb-filter”
Provides linear phase relationship
22/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter
A comb-filter of length M is an FIR filter with all M coefficients equal to one.
The transfer function of a comb-filter is
The filter is a simple accumulator which performs a moving average.
Using the formula for a geometric sum
-1--1-
)(
)()(
1
0 zX
zYzzH
M
n
n
)(
)(
1
1)(
1 zX
zY
z
zzH
M
23/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter
This can be written as
Using commutation
-2--2-
Mzz
zXzY
1
1
1)()(
1
MX[z] Y(z)11
1 z
Mz 1
MX[z] Y(z)11
1 z
11 z
24/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter-3--3-
The accumulation is done at the higher rate
The differentiation is done at the lower rate
2 registers only are required regardless of M
The filter should be properly scaled for unity gain. This can be done by dividing over M
The two’s complement number system should be used to avoid overflowing
MX[z] Y(z)11
1 z
11 z
25/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter
The advantages of a comb filter are
1. No multipliers are required
2. No storage is required for filter coefficients
3. Intermediate storage is reduced by integrating at the high sampling rate and differentiating at the low sampling rate, compared to the equivalent implementation using cascaded uniform FIR filters
4. The structure of comb-filters is very “regular”
5. Little external control or complicated local timing is required
6. The same filter design can easily be used for a wide range of rate change factors, M, with the addition of a scaling circuit and minimal changes to the filter timing
-4--4-
26/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter
A single comb filter will not give enough stop band attenuation
Cascaded comb filters can often meet requirements
The frequency response of a properly scaled M stage comb filter can be written as
-5--5-
NM
N
zz
)z(X)z(Y
1
1
11
N
S
SS )F/f(csin
)F/Mf(csin)F/f(H
M
FS/M4 cascaded comb filters
27/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Comb FilterDesign of the Comb Filter-6--6-
28/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Second Filter StageDesign of the Second Filter Stage
Better to be designed in two low pass filter stages
Stage 1 for the compensation of the droop in the passband introduced by the comb filter
Stage 2 gives the final decimation ratio and provides for the required attenuation in the stop band
MATLAB filter design and analysis tool can be used
Stage A
LPF FIR
(Compensator)
Stage B
LPF FIR
29/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Design of the CompensatorCompensator
Compensates the droop of the comb filter
Decimates by 2Fixed point filter response
Filter specifications: (FIR)
- Stopband slope (60 dB) - 5th order Inverse sinc - Passband, stopband ripple
--11--
21 taps
Symmetric FIR
30/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Design of the CompensatorCompensator--22--
Comb filter responseCompensation filter response addedCascaded response
Zoom in on passband
31/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Design of the CompensatorCompensator--33--
zoomed
constant
32/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Design of the CompensatorCompensator
Realized as polyphase structure
--44--
33/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Last Filter StageDesign of the Last Filter Stage
Implemented as an FIR LPF
Gives the final attenuation in the stopband requiredFixed point filter response
63 taps
Symmetric FIR
--11--
34/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Last Filter StageDesign of the Last Filter Stage--22--
Final frequency Response
35/36 Integrated Circuits Laboratory
Faculty of Engineering
Design of the Last Filter StageDesign of the Last Filter Stage
Realized as a polyphase filter
--33--
36/36 Integrated Circuits Laboratory
Faculty of Engineering
ReferencesReferences
1. R.E.Crochiere, L.R. Rabiner, “Multirate Digital Signal Processing”, Prentice-Hall, 1983
2. J.C.Candy, G.C.Temes, “Oversampling Delta-Sigma Data Converters, Theory, Design and Simulation”, IEEE Press, 1992
3. D.Orifino, “Designing Digital Radio Applications with Simulink®”, The MathWorks, 2002
4. “Principles of Sigma-Delta Modulation for Analog to Digital Converters”, Motorola