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Output Feedback Dynamic Surface Controller forQuadrotor UAV with Actuator Dynamics
Asad Ullah Awan
Department of Mechatronics Engineering
National University of Sciences and Technology, Pakistan
Email: [email protected]
Abstract—In this work, we develop an output feedbackaltitude-attitude controller for quadrotor UAV in the presence ofuncertainties in UAV and actuator dynamics. Controller designfor the quadrotor UAV is a difficult task due to its uncertainnonlinear dynamics. Unlike most previous works, we also con-sider uncertain actuator dynamics into the model construction ofthe UAV. For state estimation, a nonlinear observer using neuralnetworks is designed. For the controller, the dynamic surfacecontrol technique has been used, which has the advantage ofless complexity as compared to the conventional backsteppingtechnique. The closed loop stability is proved using Lyapunovstability analysis. Unlike previously published techniques, we donot assume actuator signals are available for measurement inthe observer/controller design. Simulation results are presentedto demonstrate the effectiveness of the controller in presence ofuncertainties in quadrotor UAV and actuator dynamics.
Index Terms—Quadrotor, UAV, Output feedback, Actuator,Dynamic Surface Control, Neural Networks
I. INTRODUCTION
Quadrotor UAVs are have generated alot of interest among
researchers, especially for experimental validation of algo-
rithms. This is due to the ability to perform complicated
flight maneuvers similar to helicopters while having much
simpler mechanical design. Autonomous control of quadrotor
UAV has been a subject of much research. The quadrotor
UAVs exhibit highly nonlinear dynamics, and the dynamic
charchteristics . Researchers have successfully applied a host
of control techniques to quadrotor UAV control, including
linear control [1], robust nonlinear control [2], sliding mode
control, feedback linearization [3], [4], neural network based
control [5] to name a few.
Backstepping, a widely used techinque for controlling non-
linear system in strict feedback form, has been successfully
applied to quadrotor control [6], [7]. However, conventional
backstepping has the inherent problem of ’explosion of com-
plexity’, which is caused by repeated differentiation of the
so-called virutal control nonlinear functions. To circumvent
this problem, dynamic surface control (DSC) was introduced
in [8], which introduced first-order filters, through which
the virtual control functions is passed at each step, thereby
avoiding repeated differentiations. The DSC technique was
extended to nonlinear adaptive systems using neural networks
in [9].
Most of the works [1], [2], [5], [3], [4] aimed at designing
controllers for the quadrotor UAV do not take into account
the dynamics of the actuators. By actuators, we mean the
individual motor-propeller subsystems generating the down-
ward thrusts (see Figure 1). A number of controllers for robot
manipulator with actuator dynamics have been proposed by
various researchers. In [10], [11], adaptive controllers for
electrically driven robot manipulators were proposed. In [12],
the authors have developed a fuzzy-neural-network controller
for an n-link robot manipulator to achieve position tracking in
presence of model uncertainties. Similar work in done in [13].
The adaptive output feedback DSC controllers was developed
for flexible-joint robot manipulator in [14]. In these works,
the motor dynamics were incorporated in the robot model for
the design of the controller. However, in all these works the
derived control law was a function of actuator signals such
as armature current or torque produced by actuators, which
was assumed to be measured requiring additional sensors. In
the case of the quadrotor UAV, the problem of designing an
adaptive output feedback controller for the UAV model with
actuator dynamics, without using any actuator signals such
as thrust or motor armature current, is not addressed to the
best of the author’s knowledge. In this work, we apply output
feedback DSC technique for designing stabilizing controller
for quadrotor UAV. The actuator is considered to be a motor-
propeller subsystem producing thrust. This is modeled as a first
order uncertain dynamic model, which captures the actuator
delay and conversion between armature currents and thrust.
While first order models are commonly used for DC motors,
quadrotor UAV usually employ BLDC motors. Modeling of
BLDC motors is very complicated, however, when coupled
with internal speed controllers, the system can be modelled
as a first order system [15]. To deal with uncertain terms
in both UAV dynamic and actuator models, NN’s powerful
universal approximation ability is used [16]. The NN weights
are adapted online, using the adaptation laws based on gradient
descent with the so-called ε-modification [17]. By using
Lyapunov stability theory, we arrive at conditions for obtaining
uniformly ultimately bounded (UUB) stability of the closed
loop system. Numerical simulations are used to demonstrate
the validity and performance of the proposed technique.
This paper is organized as follows. In Section 2, we discuss
the mathematical model of the quadrotor UAV with actuator
dynamics. Section 3 descibres the observer and controller
design. Section 4 provides the stability analysis, simulation
results are presented in Section 5, followed by the conclusion
in Section 6.
Proceedings of 2014 11th International Bhurban Conference on Applied Sciences & Technology (IBCAST)Islamabad, Pakistan, 14th – 18th January, 2014
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978-1-4799-2319-9/14/$31.00 © 2014 IEEE
2
X
Y
Z
zb
yb
xb
Fig. 1: The quadrotor UAV consists of four motor-propellors
generating downward thrust.
II. QUADROTOR DYNAMICS
Consider the quadrotor shown in 1. Let us define the
state vector ξ1 = [z, φ, θ, ψ] ∈ R4 to denote the altitude
and Euler angles of the UAV with respect to the inertial
frame I . Also define X = [x, y, ξ1] ∈ R6, and V =
[vx, vy, vz, wx, wy, wz] ∈ R6 denote the translational velocity
and angular velocities in body frame B. We can write the
dynamics as follows
We can write [5]
X = Ao(t)V (1)
V = fo(xo) + G+M−1U + τd (2)
(3)
The details of the terms fo(xo) can be seen in [?]. Grepresents the gravitation accelration term, M represents the
inertia matrix, which is assumed to be known and constant, Uis the force and moment input vector for the quadrotor UAV
and τd represents unknown external disturbances.
Here
Ao(t) =
[R(ξ1) 00 T (ξ1)
]
where Ao ∈ R6×6, R(ξ1) and T (ξ1) are rotation and
transformation matrices from body to fixed frame as defined in
[?]. We consider a first-order linearized actuator model with
lumped uncertainty Δa. If we introduce actuator dynamics,
we can describe the quadrotor UAV model by the following
equations
ξ1 = ξ2 (4)
ξ2 = AA−1ξ2 +Afo(ξ1, ξ2) +AG+AM−1ξ3 +Aτd (5)
ξ3 = αξ3 +Bvt +Δa(ξ3, vt) (6)
Here A ∈ R4×4, it differs from Ao in that it ignores the
terms involve vx and vy i.e. the body frame translational rates
(because they are not available for measurement), vt is the
input voltage vector to the electric motors, B is the non-
singular mapping from the electric voltages to the force and
moment vector. Also α ≺ 0. We can define fo1(ξ1, ξ2) =AA−1ξ2 +Afo(ξ1, ξ2). Here,
A =4∑
i=0
∂A
ξ1iξ2i = Γ(ξ1, ξ2) (7)
So we can finally write
ξ1 = ξ2 (8)
ξ2 = fo1(ξ1, ξ2) +AG+AM−1ξ3 +Aτd (9)
ξ3 = αξ3 +Bvt +Δa(ξ3, vt) (10)
Due to the NN universal approximation property [18], the
unknown terms fo1 and Δa can be approximated as follows
fo1(xo) � Woσo(VTo xo) + εo(xo) (11)
Δa � Waσa(VTa xa) + εa(xa) (12)
The outer weights Vo and Va are fixed, whereas the inner
weights Wo and Wa are adapted. In the following section,
the adaptive observer design with adaptive laws for the NN
weights are presented.
III. NEURAL NETWORK OBSERVER DESIGN
Suppose we define a change of variables for state estimates
ξ1 = z1 (13)
ξ2 = z2 + l1(ξ1 − z1) (14)
ξ3 = z3 + l2(ξ1 − z1) (15)
The NN based observer is defined as
z1 = z2 + l1ξ1 + d1ξ1 (16)
z2 = fo1(xo) +AG (17)
+AM−1(z3 + l2ξ1) + d2ξ1 (18)
z3 = αz3 +Bvt + d3ξ1 + Δa(xa) (19)
where l1, l2, l3, d1, d2, l3 are positive gains,
xa = [z3 + l1(ξ1 − z1), u], xo = [ξ1, z2 + l1ξ1].Due to the universal approximation property of NNs [19], we
can approximate the unknown terms as
fo1 = Woσo(VTo xo)
Δa = Waσa(VTa xa). (20)
The observer error dynamics in the original coordinates are
then as follows
˙ξ1 = ξ2 − d1ξ1 (21)
˙ξ2 = WT
o σ(V To xo) + yo +AM−1ξ3 + l1ξ1 − l1ξ2 (22)
˙ξ3 = αξ3 + WT
o σ(V Ta xa) + ya + l2ξ1 − l2ξ2 (23)
where l2 = αl2−d3+ l2d1, l1 = l1d1−d2, Wj =Wj−Wj ,
yj = WTj [σj(V
Tj xj)− σj(V
Tj xj)] + εj(xj), σj = σj(V
Tj xj)
where j = o, a.
It can be established that ||yj || ≤ kj [14].
Proceedings of 2014 11th International Bhurban Conference on Applied Sciences & Technology (IBCAST)Islamabad, Pakistan, 14th – 18th January, 2014
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A. Observer Stability Analysis
Let us consider the following Lyapunov candidate function
for observer dynamics
Vo =1
2(ξT1 ξ1 + ξT2 ξ2 + ξT3 ξ3) +
1
2tr(WT
o Wo)
+1
2tr(WT
a Wa) (24)
Taking time derivative of (24), we have
Vo = ξT1 (ξ2 − d1ξ1) + ξT2 (WTo σ(V T
o xo) + yo (25)
+AM−1ξ3 − d2ξ2 − l1ξ2) + ξT3 (αξ3 + Waσa + ya (26)
+ l2ξ1 − l2ξ2) + tr(WTo˙Wo) + tr(WT
a˙Wa) (27)
Vo = −d1||ξ1||2 − l1||ξ2|| − α∗||ξ3||+ ξT1 ξ2 + ξT2 WTo σo
+ ξT2 yo + ξ2AM−1ξ3 + l1ξT2 ξ1 + l2ξ
T3 ξ1 − l2ξ
T3 ξ2
+ ξT3 ya + ξT3 WTa σa − tr(WT
o˙Wo)− tr(WT
a˙Wa) (28)
where α∗ = −α. If we select l1 = −1 and use the following
NN adaptation laws,
˙Wo = σoξ1 − koWo (29)
˙Wa = σaξ1 − kaWa (30)
we obtain,
Vo = −d1||ξ1||2 − l1||ξ2|| − α∗||ξ3||+ ξT2 yo + ξ2AM−1ξ3+ l2ξ
T3 ξ1 − l2ξ
T3 ξ2 − tr(WT
o (σ0ξ1 − koWo − σoξT2 ))
− tr(WTa (σaξ1 − kaWa − σaξ
T3 )) (31)
Now we use the following inequalities [20], [5]
tr(WTo (Wo − Wo)) ≤ ||Wo||FWMo − ||Wo||2F (32)
||y|| < ky (33)
||a||||b|| ≤ ||a||22
+||b||22
(34)
||σ|| ≤√
No (35)
||A||F ≤ AM (36)
where (34) is the Young’s inequality. We can write
Vo ≤ −d1||ξ1||2 − l1||ξ2||2 − α∗||ξ3||2 + ||ξ2||||yo||+ ||ξ2||||ξ3||||AM−1||F (37)
+ l2||ξ3||||ξ1||+ l2||ξ3||||ξ2||+ ||ξ3||||ya||+ ko||Wo||WMo − ko||Wo||2 + ||Wo||||ξ2||
√No
+ ||Wo||||ξ1||√
No + ka||Wa||WMa
− ka||Wa||2 + ||Wa||||ξ1||√
Na + ||Wa||||ξ3||√
Na (38)
Now select the following
c1 = d1 − l22
(39)
c2 = l1 − l2 +AMo||M−1||F + 12
(40)
c3 = α∗ − AMo||M−1||F + l2 − l2 − 12
(41)
We can then write
Vo ≤ −c1||ξ1||2 − c2||ξ2||2 − c3||ξ3||2 + ||Wo||||ξ2||√
No
+ ko||Wo||WMo − ko||Wo||2 + ||Wo||||ξ1||√
No
+ ||Wa||||ξ1||√
No + ka||Wa||WMa − ka||Wa||2+ ||Wa||||ξ3||
√No + k (42)
where k =k2o
2 +k2a
2
Now completing the square with respect to ||ξ1||, ||ξ2|| and
||Wo||, we obtain
Vo ≤ −m1||ξ1||2 −m2||ξ2||2 −m3||ξ3||2 − ko4||Wo||2
− ka4||Wa||2 + k (43)
where the parameters m1 = c1 − (No
ko+ Na
ka),m2 = c2 −
No
ko,m3 = c3 − Na
kaare designed to be positive real numbers.
IV. CONTROLLER DESIGN
In this section, we present the design for the dynamic sur-
face controller (DSC) [9], [14]. The conventional backstepping
technique commonly employed to deal with nonlinear systems
in feedback form results in the so-called ’explosion of com-
plexity’ in the terms due to computation of derivative of virtual
control terms. DSC circumvents this drawback by introducing
a first-order filter in the virtual control, thereby eliminating
the need for computing the derivative. The objective of the
controller is to ensure that the trajectory error is made as small
as possible. We make the following assumption
Assumption 1: The desired trajectories ξd are bounded as:
||ξd||+ ||ξd||+ ||ξd|| ≤ M1 (44)
Define the error surface variable S1 as
S1 = ξ1 − ξd
S1 = ξ2 + ξ2 − ξd (45)
where ξd is the desired trajectory ; zd, φd, θd, ψd. The first
virtual control is designed as follows
ξ2 = −k1S1 + ξd (46)
This virtual control is passed through a first order filter as
follows
τ2ξ2f + ξ2f = ξ2 (47)
Proceedings of 2014 11th International Bhurban Conference on Applied Sciences & Technology (IBCAST)Islamabad, Pakistan, 14th – 18th January, 2014 99
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We define the second error surface
S2 = ξ2 − ξ2f
S2 = AG+AM−1ξ3 + WTo σo + l1ξ1 − l1ξ2 − ξ2f (48)
The second virtual control ξ3 is passed through another first-
order filter
ξ3 =MA−1(−AG− WT
o σo − l1ξ1 +
(ξ2 − ξ2f
τ2
)− k2S2
)
(49)
ξ3 = τ3ξ3f + ξ3f (50)
The third error surface is defined as
S3 = ξ3 − ξ3f (51)
S3 = αξ3 − αl2ξ1 +Bvt + d3ξ1 + WTa σa + l2ξ2
− l2d1ξ1 − ξ3f (52)
Finally, the true control input vt is selected as
vt = B−1((−αξ3 + αl2ξ1 − d3ξ1 − WT
a σa
+l2d1ξ1 + (ξ3 − ξ3f
τ3)− k3S3
)(53)
Define the boundary layer errors as
y2 = ξ2f − ξ2 (54)
y3 = ξ3f − ξ3 (55)
We can now write the surface error dynamics as
S1 = S2 + y2 − k1S1 + ξ2 (56)
S2 = AM−1(S3 + y3)− k2S2 − l1ξ2 (57)
S3 = −k3S3 + l2ξ2 (58)
Also the boundary error dynamics can be written as
y2 = −y2τ2+ k1S1 − ξd
= −y2τ2+Ω2(S1, S2, ξ1, ξ2, ξ3) (59)
y3 = −y3τ3+Ω3(S1, S2, S3, ξ1, ξ2, ξ3) (60)
A. Controller Stability AnalysisLet us define the Lyapunov candidate function
Vc =1
2(ST
1 S1 + ST2 S2 + ST
3 S3 + yT2 y2 + yT3 y3) (61)
(62)
Differentiating and utilizing some basic inequalities and the
fact that ||A|| ≤ AM , ||Ω2|| ≤ Ω2M , ||Ω3|| ≤ Ω3M
Vc = ST1 (S2 + y2 − k1S1 + ξ2)
+ ST2 (AM−1(S3 + y3)− l1ξ2 − k2S2)
+ ST3 (−k3S3) + yT2 (−
y2τ2+Ω2)
+ yT3 (−y3τ3+Ω3) (63)
≤ −b1||S1||2 − b2||S2||2 − b3||S3||2 − q1||y1||2
− q2||y2||2 + 32||ξ2||2 + Ω2M
4+Ω3M
4(64)
where b1 = k1 +94 , b2 = k2 − 1
4 − AM ||M−1||2 (1 + l1) −
l12 , b3 = k3− AM ||M−1||
2 , q1 =1τ2− 5
4 , q2 =1τ3−1− AM ||M−1||
2
V. CLOSED LOOP STABILITY
Define the composite Lyapunov function V
V = Vo + Vc (65)
V = Vo + Vc (66)
≤ −m1||ξ1 − (m2 − 33)||ξ2||2 −m3||ξ3||2 − ko
4||Wo||2
− ka4||Wa||2 − b1||S1||2 − b2||S2||2 − b3||S3||2
− q1||y1||2 − q2||y2||2 + Ω2M
4+Ω3M
4+ k (67)
(68)
Lemma 1: The closed loop system is unformly ultimately
bounded.
Proof: This is concluded from the afore stability analysis.
VI. RESULTS
In this section, the effectiveness of the proposed technique
on quadrotor UAV is verified via numerical simulations in the
MATLAB/Simulink environment with the Runge-Kutta ODE
solver. Table I provides the parameters used for the UAV
model. In the simulation, all inner NN weights, i.e. Wo and
Wa, are initialized to zero, while inner weights, i.e. Vo and Vaare randomly initialized from a uniform distribution between
0 and 1. Simulation sample time was set to 0.001s. In order to
demonstrate the effectiveness of the technique in the presence
of actuator uncertainities, a time varying term 0.3 sin t, was
added to the actuator dynamics. The desired trajectory for the
simulation was set as ξd := [−10 + 2 sin t, 0, 0, 0.2 sin t)].Figure 2, 3, 4 and 5 show the performance of the quadrotor
UAV during the simulation in the state variables. As is
evident from the plots, the controller yields good tracking
performance, with low RMSE (see figures). 8 shows the
estimation error of the observer for ξ1. Figures 6 and 7 show
the behaviour of the NN weights that are adapted online. The
input history in terms of voltage signals to individual motors
of the quadrotor UAV, is shown in 9
VII. CONCLUSION
In this paper, we proposed a outout dynamic surface con-
troller for a quadrotor with uncertain model and actuator
dynamics. Previous work incorporating actuator dynamics for
robot control have assumed that actuator signals are available
for measurement. In this paper, we only use the altitude and
attitude measurements for observer-controller design. Bounded
stability of the closed loop observer-controller system has
been derived via the Lyapunov stability theory. Numerical
simulation shows that the propsed technique shows good
tracking performance. In future work we hope to extend the
technique to control the x and y translational positions of the
UAV, which is not trivial due to the underactuated nature of
the UAV dynamics.
Proceedings of 2014 11th International Bhurban Conference on Applied Sciences & Technology (IBCAST)Islamabad, Pakistan, 14th – 18th January, 2014 100
5
0 5 10 15 20 25 30 35 40 45 5012
11.5
11
10.5
10
9.5
9
8.5
8RMSE =0.038538
time (in sec)
z (m
)
Fig. 2: Tracking performance of altitude z
0 5 10 15 20 25 30 35 40 45 500.02
0
0.02
0.04
0.06
0.08
0.1RMSE =0.023311
time (in sec)
φ (m
/s)
Fig. 3: Tracking performance of roll φ
TABLE I: Quadrotor UAV parameters used in simulation
Parameter Value Units
Mass m 0.586 kg
Moment of inertia about x-axis Ixx 7.5× 10−3 kg m−2
Iyy 7.5× 10−3 kg m−2
Izz 1.3× 10−2 kg m−2
Arm length l 0.165 m
Rotor inertia Jr 6× 10−5 kg m−2
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0 5 10 15 20 25 30 35 40 45 500.5
1
1.5
2
2.5
3
3.5
4
|| W
o ||F
Frobenium Norm of Wo
Fig. 6: Plot showing change in NN weights due to adaptation
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0 5 10 15 20 25 30 35 40 45 500
1
2
3
4
5
6
7
8
9
10
|| W
a ||F
Frobenium Norm of Wa
Fig. 7: Plot showing change in NN weights due to adaptation
during simulation, ||Wa||F
0 5 10 15 20 25 30 35 40 45 5012
10
8
6
4
2
0
2
Time (sec)
ξ 1
ξ1 Estimation Error
Fig. 8: NN adaptive observer performance for state ξ1, plot
showing ξ1
0 5 10 15 20 25 30 35 40 45 500
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Time (sec)
v 1
Input signal
0 5 10 15 20 25 30 35 40 45 500
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Time (sec)
v 2
Input signal
0 5 10 15 20 25 30 35 40 45 500
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Time (sec)
v 3
Input signal
0 5 10 15 20 25 30 35 40 45 500
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Time (sec)
v 4
Input signal
Fig. 9: History of inputs (voltage applied to each motor). The
input signal is limited between 0 and 5.
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