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UWB Base-band Time/Freq. Synchronization for SFO. Reporter : 黃彥欽 指導教授 : 吳仁銘 博士 2007/01/05 通訊工程研究所 國立清華大學. Outline. MB-OFDM UWB Introduction Tx / Rx Block Diagram Synchronization of SFO Time-domain effect SFO analysis Freq-domain effect Simulation Result Future Work. - PowerPoint PPT Presentation
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UWB Base-band Time/Freq.Synchronization for SFO
Reporter : 黃彥欽指導教授 : 吳仁銘 博士
2007/01/05通訊工程研究所國立清華大學
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Outline
• MB-OFDM UWB Introduction• Tx / Rx Block Diagram• Synchronization of SFO
– Time-domain effect– SFO analysis– Freq-domain effect
• Simulation Result• Future Work
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MB-OFDM UWB
• Spectrum:– 14 sub-bands– 5 band groups
f3432MHz
3960MHz
4488MHz
5016MHz
5544MHz
6072MHz
6600MHz
7128MHz
7656MHz
8184MHz
8712MHz
9240MHz
9768MHz
Band #1
Band #2
Band #3
Band #4
Band #5
Band #6
Band #7
Band #8
Band#9
Band #10
Band #11
Band #12
Band #13
10296MHz
Band #14
Band Group #1 Band Group #2 Band Group #3 Band Group #4 Band Group #5
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MB-OFDM UWB
Data Rate
(Mb/s)
Modulation
Coding Rate
FDS TDS Coded Bits/ 6 Symbols
Info Bits/ 6 Symbols
53.3 QPSK 1/3 YES YES 300 100
80 QPSK 1/2 YES YES 300 150
106.7 QPSK 1/3 NO YES 600 200
160 QPSK 1/2 NO YES 600 300
200 QPSK 5/8 NO YES 600 375
320 DCM 1/2 NO NO 1200 600
400 DCM 5/8 NO NO 1200 750
480 DCM 3/4 NO NO 1200 900
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Timing-related parameters
Parameter
Description Value
Sampling frequency 528 MHz
Total number of data subcarriers ( FFT size ) 128
Number of data subcarriers 100
Number of pilot subcarriers 12
Number of guard subcarriers 10
Total number of subcarriers used 122
Subcarrier frequency spacing 4.125MHz
IFFT and FFT period 242.42ns
Number of samples in zero-padded suffix 37
Zero-padded suffix duration in time 70.08ns
Symbol interval 312.5ns
Symbol rate 3.2MHz
Total number of samples per symbol 165
s
FFT
D
P
G
T
FFT
ZPS
ZPS
SYM
SYM
SYM
f
N
N
N
N
N
f
T
N
T
T
F
N
1
( / )
( )
s FFTf N
f
1
( / )
( )
( )
( )
ZPS s
FFT ZPS
SYM
FFT ZPS
N f
T T
T
N N
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Info. Data rate (Mbps) 53.3 80 106.7 160 200 320 400 480
Mod./ Constellation OFDM / QPSK or DCM
FFT Size 128
Coding Rate 1/3 1/2 1/3 1/2 5/8 1/2 5/8 3/4
Conjugate Symmetric Input to IFFT (FDS)
Yes Yes No No No No No No
Time Spreading Factor 2 2 2 2 2 1 1 1
Overall Spreading Gain 4 4 2 2 2 1 1 1
Data Tones 100
Info. Length 242.42 nsec
Zero-padded Prefix 70.08 nsec
Symbol Length 312.5 nsec
Channel Bit Rate 640 Mbps
Multi-path Tolerance 70.08 nsec
(The version 4/2005 post at MBOA web page)
System Parameters
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PA
2 cj f te
DataSource
P
D+PChannel encoder
Inter-leaver
Signal Mapping
GenerateTraining Symbol
AddGuard Tone
128-point IFFT
Insert Preamble
Pulse Shaping
PAPR ClippingDAC
Time-Freq Code
MB-OFDM UWB Tx
Insert Guard Interval
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MB-OFDM UWB Rx
LPFSymbol WindowControl
PacketDetection
Symbol Timing
Estimation+
Freq.HoppingSignal
ADC
Coarse carrier phase
Estimation
RemoveGuard Interval
N-pointFFT
ChannelEstimation
Channel Equalization
Pilot TrackingEstimation
Sampling ClockSync
P/SSignal
De-mapping
De-Inter-leaver
ChannelDecoder
LNA
2 cj f te
N
P
D
N
D
P
D
DecodedInformationBits
PhaseOffset
Estimation
Coarse carrier phasecompensation
s/p
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Sampling Freq. Offset (SFO)
• SFO is caused by sampling instant mismatch between DAC and ADC.
SFO , (1 )
1 sampling period
s s s s
s ss
s s
T T T T
T TT
T f
DAC ADCchannel,l ns s t r t ,l nr
T T
2T 3TT 4T
T’ 2T’ 3T’
T 2 T 3 T
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SFO Effects Simulation (Time Domain)
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Sampling Freq. Offset (SFO) (cont.)
• Effect in Time Domain
OFDM Symbol Window DriftOFDM Symbol Window Drift
0
0 symlN 1 syml N
syml N
FFT window
This leads to irreducible ISI !
max
3max
20 for UWB
40
128 37 165
6.6 10 samples per OFDM symbol
drift 1 sample after about 151 OFDM symbols
sym FFT ZPS
sym
ppm
ppm
N N N
N
Need to add/drop 1 sample after every 151 OFDM symbols !
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SFO analysis
FFTT ZPST
SYMT
FFTk S
FFT FFT
k Tf t nT n
T N= = =
{ }1
0
[ ] ( )
1 [ ] [ ] exp 2
t nTs
t nTs
l
N
kkFFT
y n y t
X k H k j f tN
p
=
=
-
=
=
= å
1
0
1
0
1 [ ] ( ) [ ]exp 2
[ ] [ ]exp 2
:
:
t nTs
N
kFFT FFT
N
n FFT
nkx n x t X k j
N N
nkX k x n j
IFFT
FFTN
p
p
=
-
=
-
=
ì üï ïï ï= = í ýï ïï ïî þì üï ïï ï= -í ýï ïï ïî þ
å
å
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SFO analysis (cont)
1
0
1
0
1[ ] [ ] exp 2 [(1 ) ]
1[ ] [ ] exp 2 exp 2 exp 2
NFFT
symkFFT FFT FFT
Nsym
kFFT FFT FFT FFT
k TX k H k j n lT
N T N
Tkn knX k H k j j j k l
N N N T
p z z
p p z p z
-
=
-
=
ì üï ïï ï= + +í ýï ïï ïî þì ü ì ü ì üï ï ï ï ï ïï ï ï ï ï ï= í ý í ý í ýï ï ï ï ï ïï ï ï ï ï ïî þ î þ î þ
å
å
{ }(1 )
'
1
0
[ ] ( )
1[ ] [ ] exp 2
t nTs
t nT lTs sym
l
N
kkFFT
y n y t
X k H k j f tN V V
p
¢=
= + +
-
=
=
= å
(1 )s s s sT T T T
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SFO analysis (cont)
'
1
0
1
'
[
0
]
[ ] exp 2
1[ ] [ ] exp
...... (
2
exp 2 exp 2
FF )[ ] T
l
N
ln FFT
N
FFT FFT
sym
FFT F
l
y n
k
FT
npY p j
N
knX k H k j
N N
Tknj j k l
n
N
y
T
p
p
p z p z
-
=
-
=
æ ö÷ç ÷= -ç ÷ç ÷çè ø
ì üï ïï ïí ýï ïï ïî þ=ì ü ì üï ï ï ïï ï ï ïí ý í ýï ï ï ïï ï ï ïî þ î þ
å
å
1444444444444444424444444444 3
{
1
0
1
0
exp 2
1[ ] [ ] exp 2 exp 2
1exp 2 [ ] [ ] exp 2
N
n FFT
Nsym
n FFT FFT FFT
sym
FFT FFT FFT
k p
npj
N
TknX k H k j j k l ICI
N N T
T knj k l X k H k j
T N N
p
p z p z
p z p z
-
¹
=
-
=
æ ö÷ç ÷-ç ÷ç ÷çè ø
ì ü ì üï ï ï ïï ï ï ï= +í ý í ýï ï ï ïï ï ï ïî þ î þì ü ìï ï ïï ï ï= í ý íï ïï ïî þ
å
å
444444
{1
0
k p
N
n
ICI-
= ¹
üïï +ýï ïï ïî þå
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SFO analysis (cont)
{ }{
{ }
1 exp 21exp 2 [ ] [ ]
1 exp 2
exp1 sin( )exp 2 [ ] [ ]
sin( )exp
k p
sym
FFT FFT
FFT
sym
FFT FFT
FFTFFT
T j kj k l X k H k ICI
T N kj
N
T j k kj k l X k H k
kT N kj NN
p zp z
p z
p z p zp z
p zp z
¹
ì ü -ï ïï ï= +í ý ì üï ï ï ïï ïï ïî þ - í ýï ïï ïî þì üï ïï ï= í ý ì üï ï ï ïï ïï ïî þ í ýï ïï ïî þ
{
{
{,
1exp 2 [ ] [ ] exp (1 ) sinc( )
;
sym
FFT FFT
FFT FFT ZPSl
k p
k
k FFT sym FFT ZPSs s
p
k p s
ICI
Tj k l X k H k j k k ICI
T N
N N NS ICI T T T T
f f f
p z p z p z
¹
¹
¹
+
ì ü ì üï ï ï ïï ï ï ï= - +í ý í ýï ï ï ïï ï ï ïî þ î þ
= + = = + = +
, is very small kkLet kf z= ×
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Residual Carrier Freq. Offset (RCFO)
• RCFO is caused by non-exact carrier freq. offset (CFO) correction before FFT.
( )/ : normalized RCFO
wher : RCFO
e
rx tx
k
FFT FFT s
f f f
f T f f
k
N
d
f z
e
e
=D × =D ×
D = -
® » + ×
PacketDetection
CFOCorrection
Coarse CFOEstimator
Symbol TimingEstimator
Remove CP FFT
Data
Preamble
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Sampling Freq. Offset (SFO) (cont.)
• Effect in Freq. Domain
1l +( )
, , , ,
, , , k
',,
where
1exp 1 sinc
: normalized residual
exp 2
ex
carrier
p 2
l k l k l k l k
l k k l k lsym k
FFT
sym k
FFT
k
k
FFT
lk kl
Y S ICI V
S j XlN
jN
lNj
N
H
k
N
X H
p f pf
e
f e z
fp
fp
æ ö÷ç ÷ç ÷ç ÷çè ø
æ ö÷ç ÷ç ÷ç
= + +
é ùæ ö÷çê ú÷= × - ×
÷çè ø
×ç ÷ê úç ÷çè øê úë û
=
» +
× ×
×
freq. offset (NRCFO)
: symbol (time) indexl
Sub-carrier Symbol RotationSub-carrier Symbol Rotation
The rotated phase is the functionof time and different between sub-carriers ! So the receiver has to track and compensate SFO and RCFO continuously in time !
k
12
N-
2
N-
l
2l +
Phase Rotation
3l +
ez
pilot
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SFO Effects Simulation (Frequency Domain)
•Timing offset in time domain resulting in phase rotation in the freq domain
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General Method
• Use Pilots to estimate SFO– Symmetrically distributed around middle subcarrier– Use the knowledge of the linear relationship between p
hase rotation of negative (C1) and positive (C2) set.
• Received pilot subcarriers
• Calculate the rotation of the pilot from this symbol to the previous
[ ] exp 2 [ ] [ ] syml l l
FFT
NR k j k l P k H k
Np z
ì üï ïï ï= í ýï ïï ïî þ
*21
*1
[ ] [ ][ ] [ ] exp 2
[ ] [ ]syml l
ll l FFT
NR k R kZ k H k j k
P k P k Np z-
-
ì üï ïï ï= = í ýï ïï ïî þ
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General Method (cont)
• Take the cumulative phase of for the two sets C1 and C2
• SFO estimation is given by
[ ]lZ k
1
2
1,
2,
( [ ])
( [ ])
l lk C
l lk C
Z k
Z k
f
f
Î
Î
=
=
å
å
R
R
2 1
2 1
2, 1,( )1
2 ( )
where ( ) is the normalization factor
l lFFT
symk C k C
k C k C
N
N k k
k k
ffz
pÎ Î
Î Î
-=
-
-
å å
å å
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Our Proposed Method
• Estimation Method– We use Least-Square (LS) algorithm to
estimate the SFO and RCFO
k
12
N-
2
N-
3,55lb+
( )intercept 3l e= +
( )slope 3l z= +
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LS estimation
• No probabilistic assumptions about data, only a signal model is assumed
• Data Model :
• Least Squares error
Signalmodel
θ
s[n]
Perturbation
NoiseModel
inaccuracies
x[n]
Signalmodel
θ
s[n]
x[n]
Error=ε[n]
Σ
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LS estimation (cont)
• LS error criterion– The value of θthat minimizes J(θ) is the LSE.
• If the signal s is linear, we can use matrix notation:
12
0
( ) ( [ ] [ ])N
n
J x n s n
12
0
( ) ( [ ] [ ])
( ) ( )
N
n
T
s H
J x n s n
x H x H
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LS estimation (cont)
1
( )
2
( )Let 2 2 0
ˆ ( )
T T T T T T
T T T T
T T
T T
J x x x H H x H H
x x x H H H
JH x H H
H H H x
• To find the minimum LS error, setting the gradient equal to error :
minˆ( )
ˆ ˆ ( ) ( )
ˆ ( )
T
T
J J
x H x H
x x H
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T
where
55 45 35 25 15 5 5 15 25 35 45 55
1 1 1 1 1 1 1 1 1 1 1 1A
é ù- - - - - -ê ú= ê úë û
Proposed Method (cont.)
( )2, 2, 2, 2,Initial 0, m m m mR Pa b *= = ×R
, , ,exp 2 sym kl k l k l k
FFT
lNS j X H
N
fp
æ ö÷ç ÷= ×ç ÷ç ÷çè ø
, 2 sym kl k
FFT
N
N
fa p=
( ), ,2lsym k
l k l kFFT
lN
N
fb p a= =
2 12
2
( )H HA A Az
be
-æ ö÷ç ÷=ç ÷ç ÷çè ø
For each subcarreier of data 64 ~ 63k =- +
2, 2 2k kf z e= × +
( )'2, 2, 2,expk k kR R jf= × -
For each instant of time 3,4,5...l =*
, 1,, *
, 1,
l m l ml m
l m l m
R R
P Pa -
-
é ù×ê ú= ê ú×ê úë ûR
( ) *, 1, , , ,(1 ) ( )l m l m l m l m l mR Pb l b a l-= × + + - × ×R
1( )l H Hl
l
A A Az
be
-æö÷ç ÷=ç ÷ç ÷çè ø
For each subcarreier of data 64 ~ 63k =- +
,l k l lkf z e= × +
( )', , ,expl k l k l kR R jf= × -
End
Enhance the BER performance by Using LS algorithm !
, 55 , 45 , 35 , 25 , 15 , 5 ,5 ,15 ,25 ,35 ,45 ,55 l l l l l l l l l l l lb b b b b b b b b b b b b- - - - - -é ù=ë û
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Simulation of using LS algorithm to estimate the slope and intercept
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SFO Simulation (without other noise)
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SFO Simulation (with AWGN & CFO)
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Sampling Frequency Offset Sampling Frequency Offset RecoveryRecovery
FFTAdd/DropADCChannelEqualizer
Pilot extraction
SFO estimator
2,l kz
l : symbol index k : subcarrier index
SFO Compensation
• Digital approach in Baseband
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Future Work
• Continue completing all the simulation• Make sure the sync. part will work successfully :
– Combine with other parts in Rx-end– Consider the multi-path effect
• Chip implementation :– Design the micro-architecture and write RTL code– Verify the system by FPGA board– Tapeout
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Thanks for your attention…