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-.
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SEQUENCE BASED RECEIVERS
FOR
BANI:lLIMITED NONLINEAR CHANNELS
by
'i1:\IAL KISHORE DUBEY. B.Sc. (Hans.). B.E.. ~l.E.
A Thesis
Submitted to the School of Graduate Studies
in Partial Fulfilment of the Requirements
for the Degree
Doctor of Philosophy
:"1c~1:.lste!"Cniversity
.June.1986
•
·..
~EQt:E:-;CE BASED RECEIVERS
: .... .
DOCTOR OF PHILOSOPHY (19861(Electrical Engineering) Hamilton, Ontario, Canada
:\lcMASTER C:-;IVERSITY
TITLE:
ACTHOR:
Sequence Based Receivers for Bandlimited ='onlinear Channels
vnlAL h.1SHORE DtiBEYB.Sc. tHons.) (t:niversity ofRajasthan, India)B.E. (Indian Institute of Science, Bangalorel~I.E. (Indian Institute ofScience, Bangalorel
.-St:PERVISOR, Professor D.P. Taylor
:-;t:~lBEROF PAGES, :w,145
,
ABSTRACT
This thesis examines receh'er stI'Uctures based on ma:umum likelihood sequence
estimation C\ILSEl for receiving quaternary phase-shift-keyed (QPSKl signals over
bandlimited. non· linear satellite channels. in the presence of additive down link gaussian
noise. Two satellite channel models are considered. In the first channel model. the effects of
intersymbol interference caused by filtenng followed by A_\l/A~l and A_\lIP~l.conversions are
taken into account while the second channel model includes a post-nonlinearity filter.
An e:<plicit e:<~ion for t.he output of the bandpass nonlinearity (BP);"U for a
QPSK signal is obtained .in terms of an ;nphase (1)-quadrature (Q) path mem?ry parameter
Pk. The computation of the output of the BP);"L requires a knowledge of its transfer-_/
characteristic. The transfer characteristics may be specified either analytically or through
experimental measurements.
An optimum MLSE ~eceiver structure for bandlimited. non-linear satellite channel
is derived and its performance e\'aluated usin.g computer simulation. Simulatirog the ~ILSE
receiver in optimum form is too time consumL"1g. so we estimated the I-Q 'Path history
parameter Pk'S by using a simple procedure analogous to decision feedback processing.
Although this method is not thecretically equivalent to an optimum computation. our results
show that it performs essentially as well as an optimum computation. For :noderate to high
S);"R. an upperbound on.the prob~bilityof symbol error is obtained. using the concept of error
events. A si::lplified expression for an upperbounci on probability of symbol error, for the case
when single-error error. e\'ents are dominant. is also obtained. A sub-opti~um reee:\'er
structure is then derived using average matched filter responses. The sub-opti~u:::1 receiver
which turns out to be a complex' filter followed by a decision device. is a relatively sim?le
'.
(..
structure.. The performllnce of the suh-optimum receiver wns estimated for two different
uplink filters. The effect of var~..ing the BPKL input drive level was also studied. Our
simulation results indicate that the performllnce of both the :'1LSE and the sub,optimum
receivers approach nsymptotically the same optimum performance band.
Finally, we extend our results .on an optimum receiver structure for receiving
QPSK signals over a digital satellite communications channel. to include the effec~s of
filtering' following the non,line,,, satellite transponder. It is 'shown that the complexity of the
:'ILSE receiver is primarily determined by the uplink chllnnel mem"ory The error perfor...mance of the reeeivcr at low sign111~to·noise ratios is evaluated by computer simulation. An
upperbound on the probability of symbol error at modera;.e to high S:\R is also obtained. .\'.
sub-optimu;" re<:eiver similar to the uplink channel filtering case is developed and its
performance evaluated using computer simulation. The deg-radation in performance of the
sub--uptimum receiver compared to the optimum :-eceiver is found to be small.
/
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I
ACKNOWLEDGEME~~S
>
I would like to e:q>ress my sincere gratitude to my supervisor. Pro(essor D.P. Taylor
for his llSsistnnc~and guidance during the course of my studies and preparation of this thesis.
I would also like to thank Professors C.R. C~ter and W.F.S. Poehlman for'serving
on the Supervisor:; Committee. Thanks are alSQ due to the E:ngirreering Word Processing
Centre for their excellent work in typing this thesis.
-l am also grateful to the Canadian Commonwealth Scholarship and Fellowship
Administration for. the support provided during the course of this research.
Last but not least. I would like to e:q>ress my·deepest thanks and appreciation to
my.wife Archana. for the innumerable sacrifices she made during the course of this
investigation. and to my son, Abhinav and my daughter. Richa. for the sacrifices they made~
unk:,owingly.
v
DEDICATED
TO
MY PAREl'iTS
VI
\
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2.7 Conclusions
ABSTRACT
ACKl"OWLEDGEMEKTS
LIST OF ILLUSTRATIOKS
-Page
iii
v
x
1
2
5
779
1113
15
17
17
19
20
~-_I
29
3030323~
~1
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TABLE OF CONTENTS
"-The 1-laximum Likelihood Sequence Recei'·er (~ILSR)2.6.1 The Complex Envelope of Received Signal2.6.2 Finite State ~1achine ~Iodel (FS~I)
2.6.3 The ~u.sRStructure
Determination ofF(Z)
The BP:"L Output for Channel ~Iemoryv = 3
•Introduction
MAXI~IUM LIKELIHOOD SEQUE:"CE RECEIVER FOR:"ON-LINEAR BANDLI~lITEDQPSK CHANNELS
The System Model,The BP:"L Output
Digital Modulation Techniques
INTRODUCTION
Scope of the Thesis
BriefReview ofMultiple Access Techniques forSatellite Communication Systems
Sources oflmpairments in Digital Satellite Communication Systems1.3.1 The Satellite Channel1.3.2 Transmitting Earth Station1.3.3 Satelli_te Repeater1.3.4 ReceiVing Earth Station
1A
1.1
1.3
2.1
2.2
2.3
2.4.. .
~ 2.5,
2.6
CHAPTER 2
CHAPTER 1
V11-
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,
, ,\./ .
TABLE OF CONTENTS
4.5 Conclusions,
Page
42
42
..,~-
46
50
51
55
56
56
5656589191
Q-..104104 ..~104104
107
109
109
109
112
119
F'
RECEI\'ERS FOR THE :SO:S·U:SEAR CHA:S:SEL I:SCLL'DI:SCPRE· A:SO POST·:SO:SLI)."EARITY FILTERI)."C
l:1troouctio:1.
St"'.l~ure :\laximum Likelihood Receiver
The System :\Iociel
Introduction
Sub-<Jptir.1Um Receiver Structures
snlt:LATIO:S OF :\lLSR A); 0 OEVELOP:\1E:ST OFSt:B-OPTI:\1U:\l RECEIVER
Receiver Performance4.2.1 The Satellite Channel :\IOOel Assumed for Simulation4.~.2 :'wtemory Requirements4.2.3 The Computations of Branch ~lctric
4.2,4 Simulation Resul~-- .
5.3
SA
5.1
4.4 Sub-optimu:n Receiver: Simulation":'04.1 Example 14.4.2 Example ~
4.4.3 Sensitivity to T\VTA input back oiT
.".~.~
, .,~.-
4,.1
CHAPTER 4
CHAPTER 3 MLSR ERROR PERFOR.\lA:SCE
3.1 Introduction
.;. 3.2 Error Events
3.3 Probability ofan Error Event
3.4 Probability ofSymbol Error
3.5 Single Error Events
3.6 Conclusions ,
----
- .
TABLE OF CONTENTS -. ..Page
CHAPTER 5 (continued)
5.5 Receiver Performance.'
5.6 Simplified Receiver
5.7 Conclusions••
CHAPTER 6 COKCLL"SIO~S ~'m SL"GGESTIO~S FOR FL"TL"RE WORK
• 6.1 Conclusions'-~
6.2 Suggestions for Future Work
APPE"DIX A DERIVATIOK OF EQL"ATIO:- (3.9)
APPE"DIX B PROCEDL"RES FOR OBTAl~IKGTHE COMPLEX FILTERRESPOKSES OF THE StiB-OPTnlt:-:-'l RECEIVERS,DEVELOPED r" CHAPTERS 2 ......:..0 5
REFERE~CES 142
,.
,
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LIIWl' OF ILLUSTRATIONS
Fig. 1.1 Comparison ofdigital modulation systems based onaverage power [41.
Fig. 1.2 Typical satellite communications system.
Fi&. 1.3 Basic stages ofa earth station.
Fig. 104 Transfer characteristics of Hughes 261-H TWT.
Fig. 1.5 .. The satellite channel model..
Fig. 2.1 Coherent demodu~tion.
,Computation of minimum branch metric for optimum :'lLSEreceiver. \' ::: 3.
Structure of the :'lLSE for a channel memorv of... = 3.") .Fig. 2.3
Fig. 2.2
Fig. 3.1 Correct path and incorrect path chosen by VA.
Fig. 3.2 An error evellt at time k1..
Fig.·U The pulse response ofa fourth-order Chebyshev filter [39J .. for2BT = 1.
Fig.4.2(a) The generic waveform FHa) for TWTA input back-off of a dB.
Fig.4.2(bl--- The generic waveform FH1) forT\VTA input back-offof a dB.
Fig.4.2(c) The generic waveform FH2) for T\VTA input back-offof a dB.
Fig.4.2(d) The generic waveform FH3) for TWTA input back-offof a dB.
Fig.4.2(e) The generic waveform FH4) for TWTA input back-offof a dB.
Fig. 4.2(:) The generic waveforr:! FH5) for TWTA input back-offof a dB.
Fig.4.2lg)
Fig. 4.2(h)
The generic. waveform n(6) for TWTA input back-offof a dB.
The generic wave~ormFH7) for T\\iTA i..,put back-offof a dB.
Fig.4.2(i) The genenc waveforr:! FHS) for TWTA input back-o::cfO dB.
LIST OF ILLUSTRATIONS (continued) ...../
Page
Fig. 4-.2(j)
Fig.4.2(k1
. Fig. 4.2(1)
Fig.4.2(m)
Fig.4.2(n)
Fig. 4.2(0)
Fig.4.2(p)
Fig. 4.3(a1
Fig.4.3<bl
Fig. 7.3(c)
Fig.4.3(d1
Fig.4.3(e)
Fig.4.3(f)
Fig.4.3(gl
Fig.4.3(h1
Fig. ~.3(i)
Fig. 4.3(j)
Fig. 4.3(k)
Fig. 4.3(1)
Fig. ·i.3{m)
Fig.4.3(nl
Fig. -*.3(0)
Fig.4.3(p)
The generic waveform Fl(9) for TWTA input back-offof 0 dB.
The generic waveform FIOO) for TWTA input back-offof 0 dB.
The generic waveform Fl(ll) forTWTA input back-offofO dB.
The generic waveform Fl(12) forTWTA input back-offofO dB.
~he generic waveform Fl(13) for TWTA input back-offofO dB.
The generic waveform Fl(14) for TWTA input b'ack-offofO dB.
The generic waveform FlOS) for TWTA input back-offof0 dB.
The generic waveform F3lCO) forTWTA input back-offof0 dB.
The generic waveform F3H11 forT'.VTA input back-offof 0 dB.
The generic waveform F3H21 for TWTA input back-offof 0 dB.
The generic waveform F3l(3) for T\\TTA input back-offof 0 dB.
The generic waveform F3H4) for TWTA input back-offof 0 dB.
The generic waveform F3l(S) for TVv"TA input back-offof 0 dB.
The generic waveform F31(6) for T\\TTA input back-off of 0 dB.
The generic wavejorm F3l(71 for TWTA input back-off of 0 dB.
The~nericwa\'eform F31l81 for TWTA input back-offof 0 dB.
The generic waveform F3H91 for T\\TTA input back-offof 0 dB.
The generic waveform F3l0Q) for T\\TTA input back-offofO dB.
The generic waveform F31(11) forT\'i'TA input back-offof 0 dB.
The generic waveform F31l 12) for T\VTA input back-oITof 0 dB.
The generic waveform F31l131 for TWTA inpu:; back-oITofO dB.;
The generic waveform F31l 14) for T\\T'TA innut back-oITof 0 dB...
The generic w::lVeform F3l11S1 for TWTA input back-offof 0 dB.
68
69"
70
71
73
74
7S
76
77
78
79
80
81
82
83
85
86
87
88
89
90
--LIST OF ILLUSTRATIONS (continued)
Fig. 4.4
Fig. 4.5
Fig. 4.6
'.
Fig. 4.7
Fig. 4.8
Fig. 4.9
Fig. 4.10
Fig. 4.11
Fig.4.12
Fig. 4.13
The ma:amum likelihood sequence receiver as simulatedfor channel memory ofv = 3.
Performance comparison ofMLSE and sub-optimum receiverfor a fourth-order Chebyshev filter with 2BT = 1.
The average generic waveform F1{(t).A} for 3 dBinput back-ofToftheTWTA.
The average generic waveform F1{(t),A} for 6 dB inputback-ofTof the T\VTA.
The average generic waveform F1{(t),A} for input bac~-ofTofOdB.
Sub-optimum receiver. defined by eqn. (4.4)
Baseband realization of the sub-optimum receiverstructure as defmed by eqn. (4.6), .
Frequency response of baseband "average" matched filterg~IFR{(t),A}.
Frequency response of baseband "average" matched filterg~IFR{(t), A}.
Performance of the sub-optimum receiver when the bandlimitingfilter consists of the cascade ofa 30% roll-ofT ;';yquistfilter and the fourth order Chebyshev filter.
Page
92~
9;
95
96
98
100 .101
10:.!
103 _
105
Fig.4.14· Performance of the sub-optimum receiver when the TWTAis operated at the input ~ack-offof6 dB.
Fig. 5.1 The satellite channel model including pre- and postnonlinearity{lltering.
Fig. 5.2 Structure of the approximate :\lLSR as simulated for an uplinkchannel memory of v = 3, and downlink memory v' = 3.
Fig. 5.3 Estimation OfPk'S using simplified procedure.
Fig. 5.4 Per:ormance comparison of the :\lLSE and the simplifiedreceiver structure for the clown-link filtering channel.
Fig. 5.5 Sub-optimum recei"er, defined by eqn. 15.221.
106
110
ll8
121
123
--LIST OF ILLUSTRATIONS (continued),
Page
Fig. 5.6
Fig. 5.7
Fig. 5.8
Baseband realization of the sub-optimum receiver structuredefined by eqn. (5.23).
Frequency res\i1lnse of the imaginary component of the basebandaverage matched filter.
Frequency response of the real component ofthe basebandaverage matched filter.
:'<111
128
129
po
I.\
SYmbol
AM-AM
AM-PM
BW
BPNL
BPSK
CDMA
DS!
E(·)
EIRP
FD~I
FDMA
F(Z)
fq(ll {(t-kTl, p0
fq .,05.'3) ({t- kT), p0
f1ll, f13ll. f1321, f133>
FSM
G(v)
a(v)
-
.'
LIST OF PRINCIPAL SYMBOLS·
Representation
Amplitude modulation to amplitude modulation
Amplitude modulation to phase modulation
Bandwidth
Bandpass nonlinearity
Binary phase shift keying
. Code-division multiple acess'
Digital speech interpolation
Error function
Bit energ:.' to noise density ratio
EfTective isotropic radiated power
Frequency Modulation
Frequency division multiplex
Frequency division.multiple access
defined on page 21
interpulse product defined on page 24
defined on page 25
defined on page 26
•defined on page 28
Finite state machine
A~1JAM characteristic ofBP:-;L
A~I!PM characteristic of BP:-;L
XIV
LIST OF PRINCIPAL SYMBOLS (continued)
Svmbol
IF
MLSE
MSK
MLSR
Ns
n(t)
Pk
Q
QPSK
RF
OQPSK
SPADE
SNR.'TDMA
TWTA
UIC
VA
Representation
Hankel transform of order 1
Intersymbol Interference
Intermediate frequency
Bessel function oforder one
Metric in MLSE
Maximum likelihood sequence estimation·
Minimum shift. keying
Maximum likelihood sequence receiver
Number of possible states of FS1>l
Noise
I-Q phase history
Inphase component -
Quadrature Component
Quarternary phase-shift-keyed signals
Radio frequency
Offset QPSK
Single channel per carrier, pulse code modulation, multiple access,demand assignment equipment
Signal-to-noise ratio
Time division multiple aCCess
Travelling wave tube amplifier
lJp-converter
Viterbi Algorithm
xv
LIST OF PRINCIPAL SYMBOLS (continued)
Svmbol
v
HPA
FFSK
h(t)
T
·Yil,Yi2,Yi3.Yi4.
,\
E
c
II n
Re [ I
, ,I I
Bi
vI
Representation
Channel memory
High power amplifier
Fast frequency shift keying
trnit pulse response of the bandlimiting filter
State of the channel at t = KT
Defmed on page 36
. Data pulse durati<>n
defined on page 136
Error event
Length oferror event
Set of allowable state sequence segments
State transition
Likelihood ratio
Element of
Super set of
Subset of
,,"orm
Real part of
:Vlagnitude
Phase of the ith transmitted pulse
One-sided white spectral density
,'lnput back-offofTWTA
,Down-link cnannel memory
XVl
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•
CHAPTER 1
INTRODUCTION
~lodern satelliq, communications systems suffer from both power and bandwidth, . .limitations. Becaus~ of the power limitation, digital satellite cO(ll!nunication systems are
normally operated with a non-linear amplifier, usually a travelling wave tube amplifier
(TWTA), in the satellite transponder. In the non-linear region of qperation, a TWTA e"hibits
both a non-linear input amplitude to output amplitude (A.\1-AM conversion) charact~ristic
and a non-linl!ar input amplitude to output phase (A.\1-PM conversion) characteristic. In
addition, because of the limited availability of satellite bandwidth, the transmitted signals
must be tightly band-limited, and this introduces intersymbol interference (lSI). The lSI
combined with non-linear amplification causes significant degradation of system
performance.
In this thesis we are concerned with the problem of developing an optimum receiver
structure and"'estlmating its performance for quarternary phase-shift keyed (QPSK)
signalling over bandlimited, nonlinear satellite channels. In deriving the receiver, the
ma;timum likelihood sequence estimation (MLSE) approach will be used, so that the receiver
. is optimum in the sense of minimizing sequence error probability on the bandlimited non-
linear channel.
A satellite must share its capacity among a large number of earth terminals. This
sharing is achieved by some form of multiple-access technique. The multiple-access problem
is fundamental to satellite communications, because it is by this means that the wide,
geographic coverage capability of the satellite channel is e:<ploited. The satellite channel
model in this thesis assumes in particular Time Di"ision :I1ultiple Accessing (TD~1AL In
1
2
oreler for us to-bring out the point that current trends are toware! using TDMA, we briefly
---describe severnl \asic multiple access techniques.
1.1 A Brief Review of Multiple Access Techniques for Satellite
Communication Systems
Commer~ialCommunicationsby satellite began officially in April 1965, when the
world's fll"st Communication Satellite INTELSAT I (known as "Early Bird"), was launched...
The fully mature phase of satellite communications probably began with the installation of
the L.'ITELSAT IV into the global system starting in 1971. The INTELSAT system serves
most of the countries of the world and has satellites over the Atlantic, Pacific and Indian
Oceans.
Frequency-Division Multiple Access (FDMAl, is one widely used multiple access
techniqu·e. In FDMA, different carrier frequencies are used for each transmitting station.,
This allows use of the same transponder amplifier until finally the overall noise level limits
the capacity of the amplifier. The presence of multiple carriers in any non-linear amplifier
produce intermodulation products which raise the apparent noise level. To reduce
intermodulation noise, the TWT drive level should be "backed-off" to avoid non-linear
operation. The carrier received power level now is less and thus the effect of thei-mal noise
generated in the earth station receiver is increased. This reduction in input drive level must
thus be optimized. Even after optimization, the effect is not trivial and the reduction in
capability ofa transponder over what it would have ifall the available information was multi-
plexed on a single carrier frequency can be as much as 6 dB. :-;evertheless, FD~IA remains a
very popular technique for high capacity transmission commercial communication satellites.
It is efficient if one is not power limited, and it is the natural expansion of terrestrial
communications methods.
)3
FDMA can be implemented in two ways. One is to multiplex, in the conventional
terrestrial manner, many channels on each carrier that is~mittedthrough the satellite.
Another is to use a separate carrier frequency for each telephone'or baseband channel within
the satellite. If many carriers are used, the intermodulation problem is still more serious. On
the other hand, it does approach, .asymptotically a li~ting level that is usually acceptable.
This sin:;le-channel per-earner approach has particular advantages in systems where there
are many links to be made, each one having only a few circuits to be handled at anyone time.. .:-<"ormal multiplexing is very convenient terrestrially but may be economical only if each
carrier has traffic, for example, in a group ofl2 channels or more.
Both systems are in extensive use today. INTELSAT uses both systems, the
SPADE (Single Channel per tarrier, Pulse Code modulation, multiple Access, Demand
assignment Equipment) being a single channel per carrier modulation-access system.
Ca'nada, Indonesia and A!geria, to mention a few, countries who use single-channel-per-
carrier sy~tems.
Time-Division :>1ultiple Access (TDMAl is the next basic technique of multiple
access. Here each earth station is assigned a periodic time slot for its transmission, and all
the earth stations use the'same carrier frequency within a periodic particular transponder. In
terms of the total satellite performance, this is the superior method because the
intermodulation noise is eliminated and. there is an increase in capacity. The required
transponder back-off is much less, just that required to achieve acceptable spectrum
spreading. T'he price paid is an increase in complexity of the g;ound equipment.. It does seem. ..
as if the long term trend will be towarcl...~ more TD1-1A since it fits natUI:ally with the
digital communications systems tJ:at are rapidly proliferating terrestrially, not only for data
transmision but more and more fo~ digitlzed voice.
r