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Research Report
University of Wisconsin-MadisonCollege of Engineering
Wisconsin Power Electronics Research Center2559D Engineering Hall1415 Engineering DriveMadison WI 53706-1691
© Confidential
2012-42
Field Weakening of a Surface Mounted PermanentMagnet Motor by Winding Switching
S. Hemmati, T. A. Lipo
Department of Electrical andComputer Engineering
K. N. Toosi University of ThechnologyTehran, Iran
Department of Electrical andComputer Engineering
University of Wisconsin - MadisonMadison, WI, US A
2012 International Symposium on Power Electronics, Electrical Drives, Automation and Motion
Field Weakening of a Surface Mounted Permanent Magnet Motor by Winding Switching
S. Hemmati Department of Electrical and
Computer Engineering
K. N. Toosi University of Thechnology
Tehran, Iran
Email: [email protected]
Ahstract-A new method for flux weakening in surface permanent magnet (SPM) machines is proposed in this paper. This method is called winding switching technique and can reliably double the field weakening speed range of PM motors. This is significant because extending the constant power speed ratio (CPSR) of SPM machines is usually challenging task due to the presence of low-permeability surface magnets and the resulting low machine inductance. In the new method of field weakening the usual three phase motor windings are separated into two portions and each portion is connected to an inverter. The paper discusses the stator winding arrangement which allows the normal and high speed operation of the machine along with the constant output power and reports simulation results taken from Finite Element Analysis.
Index Terms-PM Motors, Field Weakening, High Speed Operation, Electric Vehicle.
I. IN TRODUCTION
Permanent magnet motor drives are the topology of choice
for modern traction applications such as hybrid and electric
cars [1], [2]. The Toyota Prius is a typical example of a vehicle
using a permanent magnet motor drive in which the permanent
magnet motor is powered by a combination from a pulse width
modulated voltage source inverter. Such applications require
that the motor operate over a very wide speed range which
corresponds to a wide frequency range of the inverter. When
a permanent magnet motor is operated at a variable speed,
the internal voltage (emf) induced in the motor stator winding
increases linearly in proportion to the speed (or frequency).
Eventually, as speed increases beyond a certain point, this
induced voltage becomes greater than the voltage available
from the inverter power source. At this point the inverter is
no longer capable of feeding current into the motor since
the voltage of the load (i.e the motor) is greater than that
of the source (i.e. the inverter). Beyond this point the emf
must be counteracted by impressing a component of current
which opposes the fiux created by the permanent magnets.
This is called demagnetizing current. In other words, above
the base speed, flux weakening allows the machine to operate
in constant power. In this region, as shown in Figure 1, part
of the stator current Id (demagnetizing current) is used to
oppose the fiux from the Magnets and the Iq is used for torque
production. Below the base speed all of the stator current Iq is
978-1-4673-1301-8/12/$31.00 ©20 12 IEEE 736
T. A. Lipo Department of Electrical and
Computer Engineering
University of Wisconsin - Madison
Madison, WI, USA
Rated Torque
Email: lipo@engr. wisc.edu
Torque & Power
--_._----_._----_._---_.,
� 1\.\ P Rated
Power ··'·" .. T .... " ... _ ..... :
Iq & Id Rated ........................ ...
Current , .
•.•..
Iq
: .
................... .
,
,
,
Speed �------��----------�----�
Base Speed Max Constant
Power Speed
Fig. I. Constant power and torque operating region.
used to produce constant torque and the Id is equal to zero in
this region. The ability of a demagnetizing component varies
with the design of the motor and a maximum speed beyond
the point at which field weakening begins can typically only
be extended to about twice or three times the onset of field
weakening.
Several authors have addressed flux weakening in PM ma
chines, [3]- [5] and [6]. The traditional FW method, which
is accomplished by applying a large demagnetizing current in
the d-axis of the PMs [3], is a way of weakening the air-gap
magnetic field and enlarge the constant-power operating range;
however, FW obtained by this method increases the winding
copper losses and also risks irreversible demagnetization of
the PMs. In [4], the main design criterion for optimal fiux
weakening has been presented. The purpose of this criterion
is to make the magnet flux linkage equal to the d-axis stator
flux linkage (valid for both smooth air gap and salient-pole
machines). An improved method to extend the constant power
speed range of the brushless dc motor using dual-mode inverter
+
Fig. 2. Circuit diagram of the concept.
Fig. 3. Circuit diagram of Normal operation - Current directed into the dots.
control has been proposed in [7] and verified experimentally in
[8]. This method combines both the phase-advance technique
and back-to-back thyristors in each phase. The reason or
justification for using back-to-back thyristors, as described
by the authors, is that the thyristors block the conduction
of the anti-parallel diodes. This eliminates the regenerative
torque component produced by the diodes conduction, hence
increasing the net torque and power produced by the machine.
Most hybrid vehicles require a field weakening range of 5-6
to l. Thus permanent magnet machines with only an inherent
2 or 3 to 1 field weakening range using demagnetizing current
can be employed as a motor for a hybrid vehicle. Machine used
today such as the Prius realize their 5 to 1 field weakening
range by intentionally introducing extra leakage inductance
into the machine. The approach inherently makes the machine
larger and heavier than would be necessary for the purpose of
simply providing the necessary torque.
In this paper a new configuration of stator windings is
proposed. Our goal is to extend the constant power speed
in PM motors up to about 4 times the base speed without
using the demagnetizing current. Since most well designed,
and optimized machine fall into the category of 2-3 to 1 field
weakening ability this new strategy could be an important
control function which would allow well designed machine
with minimum size and weight to be used for this application.
II. ANALYSIS OF SPM WI T H NEW WINDING
CONFIGURATION
Figure 2 shows a circuit diagram of the concept. The usual
three phase motor windings are separated into two portions,
portion 1 (left half portion on Figure 2) and 2 (right half
737
+
----+ --+
Fig. 4. Circuit diagram of High speed operation - Current reversed in half of the three stator winding.
portion on Figure 2). Both ends of the windings are brought
out of the machine, resulting in 3x4 or 12 leads. Three of
the leads from portion 1, normally forming the input of three
phase winding are connected to one inverter. Also the three
of the leads from portion 2 ( i.e the dot ends of portion 2)
are connected to a second inverter. The other 6 leads are now
connected together in each phase to form the mid points. These
mid points are now connected to three thyristors as shown
in Figure 2. As an alternative to thyristors, three contactors
could also be used. Figure 3 shows the resulting circuit when
the three thyristors are turned on during normal low and
moderate speed operation. In this case the three thyristors that
are turned on form a wye connection for portion 1 and also
for the other portion. In this case the currents on both the
right half and left half of the split three phase windings are
directed into the "dots" indicating that the flux produced is in
an additive polarity meaning that the flux produced in each
pole by each of the winding halves are additive. In this case
the voltage induced into each half of the winding from the
rotating magnets is also additive resulting in normal low and
moderate condition. In Figure 4 is shown the situation when
the three thyristors are turned off (or contactors are opened).
It should be noted that now the currents flowing into the right
half portion of the three phase windings (portion 2) are flowing
out of the dots rather than into the dots. This means that the
fluxes produced by the two windings are subtractive rather than
additive. While some net flux is produced, it is substantially
less than when the winding fluxes are additive. However, most
importantly, the voltage induced into the two portions of the
phase windings are also subtractive consequently reducing the
emf and alleviating the condition wherein the internal voltage
is beginning to exceed the terminal voltage provided by the
two inverters.
A brushless surface mounted permanent magnet ac motor is
considered as a simulation drive motor in this paper. This is an
eight-pole motor that operates up to about 6000 rpm. Figure 5
shows the cross-section and the basic dimensions of the motor.
It has to be mentioned that the basic dimensions of simulated
motor is as same as the Prius 2004 motor. The only difference
is that the non-IPM type as well as double layer winding for
the stator is considered here. Figure 6 shows the lap winding
configuration of phase A in which the q = 2 slots/pole/phase.
Basic dimensions [mm] Outer stator dia.: 270.0
Inner stator dia.: 162.0
Inner rotor dia.: 110.0
Outer rotor dia.: 160.6
Air-gap length: 0.7
Axial core length: 100
Magnet thickness: 6.54
Fig. 5. Basic dimension of the drive motor.
Fig. 6. Two layer lap winding of stator phase A.
The normalized air gap MMF produced by current flow in the
winding of one of the three phases (phase A) in the low speed
operation, is shown in Figure 7(a). Assuming for simplicity
that 112 amp flows in the coils of the winding, the amplitude
of fundamental component of the MMF can be calculated as
2 17r 1 2 1 5(;' 1 2 y'3 FI = - (-)sin(¢)d¢+- (-)sin(¢)d¢= -+-'if 0 2 'if ]' 2 'if 'if
Figure 7(b) shows the MMF that is produced when the
current is reversed in half of the three stator windings. In this
case the amplitude of fundamental component of the MMF
reduces to
2 Jif 1 1 F2 = - ( -)cos( ¢) d¢ = -'if � 2 'if -"6
The ratio of the MMF for the case of Figure 7(a) to the
MMF of the case of Figure 7(b) becomes
. F2 1 Ratw = -= 2 7r V3 = 0.268 FI 7r + 7r
Because of this change of current flow it can be shown that the
synchronous reactance as well as the induced EMF also drops
by the same amount, i.e. 0.268. Figures 8 shows an example
of this situation in terms of phasors. The per unit synchronous
reactance of the machine at rated speed is 0.86 and the emf
738
: ................................................................................................................................................................ .
MMF A
112 o n/6 5n/6
l ............................................................................. (.iif ............................................................................ ,
(b)
Fig. 7. Normalized MMF distribution of stator phase A winding assuming 112 amp flows in the coils at (a) normal and (b) high speed operation condition.
Vs= 1 Xs1s= l.72
I.� O.875 i7S I 1qs=0.5 E= 2 I I
d-axis (a)
q-axls -+-
X,1s= 046
.
21:S=0.7
___ +X1S I E=0.53 1s=l
I d-axis (b)
Fig. 8. Phasor diagram for operation at 2 pu speed: (a) before and (b) after the switching event.
at rated speed assumed as 1.0. The parameters of machine are
given in the Appendix. At two per unit speed the synchronous
reactance will rise to 0.86*2.0 = l.72 per unit while the emf
will rise to 2.0 per unit. The vector diagram of Figure 8 (a)
will exist in which the torque producing component of the
current has dropped to 0.5 pu and hence the torque drops to
0.5 per unit such that the power remains at 0.5*2.0 = l.0 per
unit. At this point the reactive component of current has risen
to -0.875 per unit, nearly the maximum permissible value of
-1.0 per unit. If the speed continue to rise just above 2 per unit
the reactive component will equal 1 and the torque producing
component to zero. At this point the power drops to zero and
the motor is unable to accelerate further.
Figure 8(b) shows what happens when the thyristors are
4oo,-----�----�_,--------�--�--------, - At 1500 rpm (MTPA) 350
300 -
250
........ At 3000 rpm and before switching event _._.- At 3000 rpm and after switching event
E : : : :Z : : : -; 200 : : : ::::s I I I
! 150 .... ............... ... , •••• J., ..... �'I,. ••• \.-••• � ..... \ ••••• �'" ••••• , ••••• � ..... �l, .... '" .............................. i, .... .. .
" .........• _ ,- • .- • r r . ....
.... ..". ... .. ... � ..... 'r ... :.� • , , , , , , , , , , , , , , , , , , 1 00 �:;.�.�:..---;:,:;�":;.�.�;,---.r�:.;.�,,.:;�.�:..:\.;.�:.;�.\.:;��.�:\:;.�;.:;.,.r�;
.�-':;�;..�:,.;.-,;;.�.,:,;�;..
50 -
OL-----�----�----�----�------�----� o 10 15 20 25 30 Time (ms)
Fig. 9. Torque at 1 per unit speed (1500 rpm) and 2 per unit speed (before and after switching event).
suddenly turned otf. Now the emf and the synchronous reac
tance drops to 0.268*2.0 = 0.53 pu and 0.268*1.72 = 0.46 pu
respectively. The phasor diagram shows that the component of
current needed to provide demagnetizing mmf (d-axis current)
now drops to zero while the torque producing component
becomes 1.0. The output power is now E*I = 0.53* I = 0.53 per
unit. This condition now allows the speed to increase beyond
2.0 per unit.
III. SIMULATION RESULTS
The Ansoft-Maxwell package was used for running sim
ulations. The machine was simulated in different operating
points starting from 1500 rpm up to end at 5600 rpm. Figure 9 shows the electromagnetic torque developed by the machine at
nominal speed 1500 rpm and also at twice nominal speed 3000
rpm befor and after switching event. At the nominal speed
machine is operating in maximum torque per amp (MTPA),
in which the input stator current vector is aligned with the
q-axis. Before switching event when the machine is operating
at 3000 rpm the torque is the half of that in nominal speed
and the angle between current and q-axis is now 60 degrees.
Figure 8(a) shows this situation in terms of phasor. When the
thyristors are suddenly turned off, the torque is decreased to
about 84 N.m. This was predictable, because it was already
shown that after switching event the flux is weakened by 0.268
in compare with the case of operating at nominal speed, so the
torque drops by that factor to 310*0.268 = 83.08 N.m. Table 1
shows the simulation result for all operating points. It can be
seen in table 1 that after switching event the input voltage is
120 volts. Now this voltage can be increased and this makes
the speed to increase up to 1500/0.268 = 5600 rpm. In the new
field weakening region the torque is constant and the output
power is increased as the speed is raised by increasing the
input voltage. In fact after switching the windings the field is
weakened so that the back-emf is decreased enough and this
situation allows the speed to goes up till 5600 rpm (3.73 per
unit).
739
TABLE I FEM MODEL RESULTS
Speed [rpm] 1500 3000 3000 (FW) 4500 5600 Torque [N.m] 310 155 87 87 87
Vph (Inv I +Inv2) [V] 230 176 120 180 230 Iph[A] 95.45 95.45 95.45 95.45 95.45
Power Factor 0.77 I 0.86 0.86 0.86 Pout [KW] 48.69 48.69 27.33 40.99 51
Etliciency [%]
300 E � 200 � E" {:. 100
9l.6 92.2
°0L---�20�0�0---4�0�00------::-:'6000
50 .. _� __ ... , .. [ 40 ----------,--- -i ---�,���-� 30 �,/
a. '[20 ---------->---
:; 010 OL---�--------�
o 2000 4000 Speed [rpm] 6000
88.2 88.2 85.9
� 250 ,---------�------, � .'''' : ,� � 200 , ------�----/----'; '-, j,---:§. 150 ---------------1---'- .-------
'0 � ...... : E 100 g 50 ---------------------'---� 0 L-__ --:-::-:--__ :-:':-:: __ ____::_:' a. 0 2000 4000 6000
C ,.. g . ·u E UJ
100 80 ..----.... ---� ... ---.
60 40 20
OL---�--------� o 2000 4000 Speed [rpm] 6000
Fig. 10. Torque, Output Power, Input Voltage and Efficiency V s. Speed.
In Figure 10 the torque, voltage, output power and efficiency
vs speed for all simulated operating points from 1500 rpm up
to 5600 rpm are shown . In this figure it can be seen that in
the new field weakening region the torque produced by the
machine remains constant whereas the output power increases
as the speed goes up. The amount of power delivered at the
output at 5600 rpm now is as same as the power at nominal
speed. This means that the maximum constant power speed is
extended up to 3.73 times the nominal speed. It should be
noted that in this point there is no demagnetizing current.
In other words, this is the maximum speed without using
the demagnetizing current. It can be shown that using the
demagnetizing current allows the speed to increase beyond
the 4 per unit speed.
IV. CONCLUSION
The winding switching method has provided a convenient
way of extending the machines constant power operating
range. The analysis and simulation result has shown that
The maximum CPSR achieved using this technique without
using the demagnetizing current is 3.73: 1. This is significant
because the traditional field weakening method obtained by
demagnetizing current increases the winding copper losses
and also risks irreversible demagnetization of the PMs. Using
demagnetizing current allows the speed to increase beyond the
4 per unit speed.
ApPENDIX
Machine parameters and specifications is provided in table
2.
TABLE IT MACHINE SPECIFICATION AND PARAMETERS
Base Speed Rated Torque Phase voltage Line Current Stator slots
Number of poles Stator turn per coil
Stator phase resistance D and Q axis inductance
Magnet residual flux density
REFERENCES
1500 rpm 310 N.m
230 V 95.45 A 48 slots 8 Poles 8 Turns 0.13 S1
3.31 mH 1.1 tesla
[I] Y. Dai, L. Song, and S. Cui, Development of PMSM drives of hybrid electric car applications, IEEE Trans. Magn., vol. 43, no. 1, pp. 434437, Jan. 2007.
[2] X. Yanliang, X. Jiaqun, W. Wenbin, and T. Renyuan, Development of permanent magnet synchronous motor used in electric vehicle, in Proc. 5th Int. Can! Elect. Mach. Syst., 2001, vol. 2, pp. 884887.
[3] T. M. Jans, Flux-weakening regime operation of an interior permanentmagnet synchronous motor drive, IEEE Trans. Ind. Appl., vol. IA-23, no. 4, pp. 681689, Jul. 1987.
[4] R. F. Schiferl and T. A. Lipo, Power capability of salient pole permanent magnet synchronous motor in variable speed drive applications, IEEE Trans. Ind. Applicat., vol. 26, pp. 115123, Jan. Feb. 1990.
[5] T. Sebastian and G. R. SIemon, Operating limits of inverter-driven permanent magnet motor drives, IEEE Trans. Ind. Applicat., vol. 23, pp. 327333, Mar.Apr. 1987.
[6] B. Sneyers, D. W. Novotny, and T. A. Lipo, Field weakening in buried permanent magnet Ac motor drives, IEEE Trans. Ind. Applicat., vol. 21, pp. 398407, Mar.Apr. 1985.
[7] 1. S. Lawler, 1.M. Bailey, and 1.W. McKeever, Extended constant power speed range of the brushless DC motor through dual mode inverter control, , Oak Ridge National Lab., UT-Battelle, LLC, 2001.
[8] 1. M. Bailey et aI., Dual mode inverter control test verification, , Oak Ridge National Lab., UT-Battelle, LLC, ORNUTM-20001172, 2001.
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