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Saturation Issue with TGC Sensors from B. Lefebvre, V. Smakhtin and B. Vachon, April
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Outcome from the VMM/sTGC Workshop at Weizmann Institute
May 14-15, 2015Gianluigi De Geronimo
Brookhaven National Laboratory, Upton, NY
Acknowledgement Brigitte Vachon, Vladimir Smakhtin, Alex Vdovin, Nachman Lupu, Benoit Lefebvre,
George Mikenberg, Lorne Levinson, Daniel Lellouch, Venetios Polychronakos
May 22nd, 20151
Saturation Issue with TGC Sensors
from B. Lefebvre, V. Smakhtin and B. Vachon, April 2015 2
Saturation Issue with TGC Sensors
from B. Lefebvre, V. Smakhtin and B. Vachon, April 2015 3
Saturation Issue with TGC Sensors
from B. Lefebvre, V. Smakhtin and B. Vachon, April 2015 4
Saturation Issue with TGC Sensors
from B. Lefebvre, V. Smakhtin and B. Vachon, April 2015 5
Front-End Circuit
CA1 output
CA1 CA2 CA3
BLH
SH
Shaper outputadaptive resets
with PZ cancellation
CA1, CA2, CA3 provide charge (current) amplification before shaperAmplification is required for noise, and it is programmable
6 from G. De Geronimo, December-April 2015
TGC 200pF 2pC
iin
Qin
CA1
CA2
CA3
out 500mV + tail
2pC
7 from G. De Geronimo, December-April 2015
iin
Qin
CA1
CA2
CA3
out 900mV no tail
4pC
saturation
baseline tail (several µs)
TGC 200pF 4pC
8 from G. De Geronimo, December-April 2015
9
Qout = Qin ·NQin
-∞
CF CF·N
N1
Ibias
-∞
N1
Ibias
sp
sp
sp
sn
sn
sn
from sensor
to virtualground
Dual-Polarity Charge Amplifier
from G. De Geronimo, December-April 2015
τF Correction for Type 1 Dead Time
500 fC @ 200ns
Output
CA1
2pC
Solution: CA time constant τF ~1/10 by modifying size of feedback MOSFETs
in saturation deadtime limited to sub-µs
10 from G. De Geronimo, December-April 2015
Origin of Type 2 Dead Time ?
from B. Lefebvre, V. Smakhtin and B. Vachon, April 2015 11
AC-Coupled Charge Amplifier
CAC = 100 pF
CDET = 100 pF
RDET = 10 MΩ
Charge signals
Ideal charge amplifier
Ideal charge amplifier with AC-coupled charge signals
12
AC-Coupled Charge Amplifier
ICAC (input current through CAC)
Charge amplifier output
Response of charge amplifier to AC-coupled charge signals
t = RFCF
200µs
13
AC-Coupled Charge Amplifier
ICAC (input current through CAC)
Charge amplifier output
Response of charge amplifier to AC-coupled charge signals
t = RFCF
10µs
Detail
14
AC-Coupled Charge Amplifier
ICAC (input current through CAC)
Charge amplifier output
Response of charge amplifier to AC-coupled charge signals
10µs
sRDETCAC
1 + sRDET(CDet+CAC)Transfer function =
(derivative of exponential decay)
Detail
15
AC-Coupled Charge Amplifier
ICAC (input current through CAC)
Charge amplifier output
Response of charge amplifier to AC-coupled charge signals
10ms
t = RDET(CDet+CAC)
sRDETCAC
1 + sRDET(CDet+CAC)Transfer function =
Detail
16
AC-Coupled Charge Amplifier
Charge amplifier output: zero-area response
Response of charge amplifier to AC-coupled charge signals
10ms
17
AC-Coupled Charge Amplifier
Charge amplifier output: zero-area responseNegligible dependence on rate: 10kHz and 100kH compared here
Response of charge amplifier to AC-coupled charge signals
10ms
18
The front-end electronics has to be able to cope with these shifts
AC-Coupled Charge AmplifierResponse of charge amplifier to AC-coupled charge signals
10ms9.3ms
Detail
19
Charge amplifier output: zero-area responseNegligible dependence on rate: 10kHz and 100kH compared here
The planned decrease in time constant will partly reduce the positive shift
20
Qout = Qin ·NQin
-∞
CF CF·N
-∞
N1
Ibias
from sensor
to virtualground
VMM1/2 Charge Amplifier for Positive Charge
DC source to bias mirror and recharge input node ~500pA
A non-linear asymmetry exists in MOSFET-based integrated front-ends
AC-Coupled VMM1/2 Front-End
CAC = 470 pF
CDET = 100 pF
RDET = 10 MΩ
Charge signals
VMM1 FE
Actual charge amplifier with AC-coupled charge signals
Ideal Filter
amplifier
adaptive resetleakage current
Iout
CAout
SHout
21
Voltage amplifier output (CAout)
Response of charge amplifier to AC-coupled charge signals
200µs
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
22
Voltage amplifier output (CAout)
Response of charge amplifier to AC-coupled charge signals
10µs
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout): note pole-zero cancellation
Shaper output (SHout)
Detail
23
Voltage amplifier output (CAout)
Response of charge amplifier to AC-coupled charge signals
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
10kHz, 1pC, leakage 500pA
24
Voltage amplifier output (CAout)
Response of charge amplifier to saturating AC-coupled charge signals
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
10kHz/1kHz, 1pC/10pC, leakage 500pA
25
Voltage amplifier output (CAout)
Response of charge amplifier to saturating AC-coupled charge signals
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
10kHz/1kHz, 1pC/10pC, leakage 5nA
26
An increase in DC leakage current alleviates saturation
Voltage amplifier output (CAout)
Response of charge amplifier to AC-coupled charge signals
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
10kHz/1kHz, 1pC/10pC, leakage 50nA
27
The increase in DC leakage current can be high, but it increases the noise na it may eventually limit the dynamic range
Voltage amplifier output (CAout)
Response of charge amplifier: higher charge and rate
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
100kHz/10kHz, 2pC/10pC, leakage 50nA
28
Voltage amplifier output (CAout)
Response of charge amplifier: higher charge and rate
30ms
AC-Coupled VMM1/2 Front-End
Charge amplifier current output (Iout)
Shaper output (SHout)
100kHz/10kHz, 2pC/10pC, leakage 50nA
Detail
29
29.3ms
Solutions Being Integrated• Decrease discharge time constant for fast recovery from
saturation and high-rate operation• Double size of feedback capacitance to reduce voltage swing• (Implement switchable DC current)• Modify feedback for dynamic compensating current
Qout = Qin ·NQin
-∞
CF CF·N
N1
-∞
N1
Ibias
from sensor
to virtualground
compensating current Replica to preserve
pole-zero cancellation
30
Note: work in progress
Description of experimental setup and observations made at the Weizmann Institute on 15 May 2015.
1) Readout of small sTGC prototype strips
2) Readout of Module-1 sTGC pad
31 from Brigitte Vachon and Vladimir Smakhtin, May 2015
1) Readout of small sTGC prototype strips Small 10x20 cm2 prototype sTGC with strips on both sides. Chamber operated at nominal operational HV of 2.9kV Look at signals from Sr-90 radioactive source (rate ~ 10 kHz)
+HV
G10
G10
wiresgraphite
graphite
strips
strips
32 from Brigitte Vachon and Vladimir Smakhtin, May 2015
Observed change in efficiency as function of current injected into the VMM1
Efficiency observed to reach maximum for current of approximately 60 nA.
1) Readout of small sTGC prototype strips Use VMM1 readout
Look at VMM1 analogue pulse Gain = 0.5 mV/fC, Peak Time = 25 ns, Neighbour channel = off
Use pull-up resistor (20 MΩ) on sTGC adaptor board to inject small variable current into VMM1.
VMM1
+ 2 V
20 MΩ
33 from Brigitte Vachon and Vladimir Smakhtin, May 2015
1) Readout of small sTGC prototype strips Recorded raw signals from strips on opposite side of the detector Raw signals used as input to Gianluigi's simulation
Raw signalChannel 4
50 Ω
+ 2 V
20 MΩ
Strip on top cathode
Strip onbottom cathode
OscilloscopeAgilent, MSO-X 4054A
VMM1 analog output, Channel 2
34 from Brigitte Vachon and Vladimir Smakhtin, May 2015
35
1) Readout of small sTGC prototype strips
Raw stripsignal from small 10x20 cm2
prototype
VMM1 analogueoutput
35 from Brigitte Vachon and Vladimir Smakhtin, May 2015
2) Readout of sTGC Module-1 pad Chamber operated at nominal operational HV of 2.9kV
Look at signals from Sr-90 radioactive source (rate ~ 1-3kHz) Readout pad with VMM1
Look at VMM1 analogue pulse Gain = 0.5 mV/fC, Peak Time = 25 ns, Neighbour channel = off
Use pull-up resistor (20 MΩ) on adaptor board to inject small variable current into VMM1.
Observed change in efficiency as function of current injected into the VMM1 (optimal value observed to be approximately +60nA)
Record VMM1 analogue pad readout using +2 V DC on 20 MΩ pull-up resistor (from ~1V input equals to ~60nA).
36 from Brigitte Vachon and Vladimir Smakhtin, May 2015
2) Readout of sTGC Module-1 padSr-90 source
VMM1
+2 V DC on 20 MΩ pull-upresistor
37 from Brigitte Vachon and Vladimir Smakhtin, May 2015
38
VMM1 analogueoutput
2) Readout of sTGC Module-1 pad
38 from Brigitte Vachon and Vladimir Smakhtin, May 2015
Note from Vladimir Smakhtin
39
"During the meeting we have measured signals from strip 10x20 cm2 sTGC.
- after optimization Voffset from 1.2V to 2V value by eye we achieved 100% efficiency at operation HV=2.9kV and rate per channel ~ 3kHz,- for this test we are using original method for strip efficiency using two identical up and down strips- we have protocol and raw files( full set which needed for modeling and simulation)
After mini meeting we started tests with Module-1 and pad.
- alignment of Co-60 and optimization of Voffset using scope have been completed- developing method for measure rate and efficiency- we have some very preliminary results- the results of this activity will be reported in a next meeting"
40
Pad capacitance
Amplifier-Shaper-Discriminator Ics and ASD boards, October 1999 (and re-calculated for sTGC)
[Note: Largest pad: Area = 470 cm2]
C PG=710 pF (measured )
C PW=(0.30 pF/cm 2)× A pad=50 pF
C PP=0 pF (measured )
C PH=(0.15 pF/cm 2)×Apad=25 pF
C PC=k ϵ0 Apad
d∼3500 pF
k∼4.7ϵ0=8.854×10−12 F/md=0.1 mm
ϯ
ϯ
ϯϯ
ϯϯ
Example: Area = 164 cm2 (pad 7)
Taken from: https://indico.cern.ch/event/371991/contribution/1/material/slides/0.pdf
0.2
mm
+HV
1.5
mm
G10
G10
CPW
CPGCPP
CPH
pad-to-padvia honeycomb
CPC
from Brigitte Vachon and Vladimir Smakhtin, May 2015
41
sTGC cross-section
J. Oliver, “ATLAS Muon New Small Wheel Grounding, Power and Interconnect - Guidelines and Policies”,
https://edms.cern.ch/file/1428856/1/NSW_Grounding_Architecture_v2_20150202_PDR.pdf
from Brigitte Vachon and Vladimir Smakhtin, May 2015
Additional Discussions 1/2
from Nachman Lupu, May 2015 42
Average rate as high as 1MHz
Capacitance as high as 2nF
Additional Discussions 2/2• Acquisition reset (soft reset)
• Done at falling edge of ENA• Configuration from SCA (CS,CK,DI,DO)
• SPI in chunks of 96 bits• Use one of 96 bits to generate global reset (hard reset)• CS active low (to be confirmed)
• SEU mitigation• Use DICE or similar for registers• Use TMR for state machines
• Direct 6-bit output dead time• Same as high-resolution in simultaneous mode
• Need for L0 buffers and selection logic in VMM• May be moved off-chip and replaced with double, higher
bandwidth data lines (4 x 320MHz, DDR)
43
Issue Circuit Solution Status Complexity
VMM3 Priority
Schematics
Layout
TGC saturation: high-charge, high-rate
Front-end Fbk time const., fbk capac., dynamic current
in prog. mid high in prog. in prog.
MSB accumulations in 10-bit and 8-bit ADCs
ADC decision nodes, PSR
TBD queued mid high
Data repetition Token/FIFO logic Token-reset, FIFO alignment in prog. mid high in prog. in prog.
High-rate efficiency (discrim.) Shaping amplifier Bipolar resp. (SLF bypass) in prog. low high in prog. queued
BCID consistency Gray-code counter Clock inversion done low high done done
Direct timing enable Control logic Logic inversion done low high done done
Event loss from ADC reset Channel logic Logic fix and routing in rpog. low high done in prog.
Threshold bit error Channel logic Logic fix done low mid done done
DAC compression FET compression MOSFET size and biasing done low mid done done
Pulser rise-time, noise Injection switch Size optimization done low mid done done
Counter turnaround Counter cells Re-routing done low mid done done
Front-end disabled in negative mode with SFM low
Front-end TBD queued low mid in prog. in prog.
High baseline channels Baseline stabilizer Increase BLH current meas. low low queued
Buffer float at bypass Buffer input stage Add switch simul low low done done
Decay time in peak detector in analog readout mode
Leakage hold node Dual front-end circuit for voltage and current-mode
simul mid low queued
Fixes (May 2015)
44
Function Circuit Notes Status Complexity
VMM3 Priority
Schematics
Layout
TGC pads 2nF Front-end See also recovery from saturation in prog. mid high in prog. in prog.
Simultaneous high-res. & direct-out
Channel and control logic
Channel reset defined queued mid high
Single-ended config. IOs Interface 1.2V logic queued low high
Double data-out lines/rate Interface 4 SLVS diff. output lines, 320 Mb/s DDR queued low mid
SLVS IOs Digital IOs Standard 200mV +/- 200mV in prog. low mid in prog. queued
Latency reduction in analog path
Shaping amplifier
Optional order reduction queued mid mid
Latency reduction in digital paths
Readout logic
Concerns latencies for direct and slow outputs (ck-to-data)
queued mid mid
Timing ramp optimization Analog TAC Reduce from 125ns to 65ns done low mid done done
Configuration interface Interface SPI 96-bit w/reset bit queued mid mid
Synchronous ART flag ART logic Flag synchronous with ART clock hold low mid
SEU-tolerant logic Registers & control
Configuration and state, DICE static + TRM state
queued mid mid
Timeout circuit Analog TAC Timeout if no ramp-stop within 1µs queued low low
L0 handling logic Readout See Lorne's document hold
Improvements (May 2015)
45
Conclusions• Saturation in VMM1/2 has been observed with TGC
prototypes• component due to amplitude saturation and long discharge time
constant in charge amplifier - will be addressed with decrease in time constant, increase in feedback capacitance and, if required, fast recovery feedback
• component due to shift in charge amplifier output baseline from ac-coupling - will be addressed with increase in feedback capacitance, dynamic compensation current and, if required, programmable dc leakage current
• workaround with injected dc current alleviates saturation, being tested at Weizmann
• saturation type 2 indicates existence of ac-coupling in detector signal path
• VMM3 design revision in progress, target July 2015• we will integrate high and medium-priority items; low-priority items as
time allows• very limited time to compete the tasks, which increases risks46
Backup Slides
47
Q
Rs
Cs
xN QxN
xN
charge amplifier
shaper
Charge Amplifier Detail
· simplified schematics· positive charge circuit
pole-zero cancellation(charge gain = N)
CF ≈ 2.3 pF
amplitude ~ Q/CF
time constant τF from size of MF and amplitude
MF
F
P
F
PFeargdisch e600CkT
21ENC
from non-stationary noise
48