Milimeterwave Patch Antenna

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    TECHNOLOGY FORCES (Technol. forces): Journal of Engineering and Sciences January-June 2010

    Abstract In this paper we present millimeterwave

    patch antenna designs for medical implants. The

    designs are based on the transmission line model and

    are simulated in CST. We first present a 31.5GHz

    patch antenna design based on a RT6002 substrate (

    =2.94 ). The antenna has a small form factor and

    exhibits a high return loss and directivity. However,

    it does suffer from high attenuation loss and cannot

    be used for deep tissue implants. We next propose a

    5.85 GHz design that is based on a super-high

    permittivity substrate ( = 80). This design retains

    the small size of the 31.5GHz antenna but greatly

    improves the link budget. This improvement can result

    in greater data bandwidth or higher penetration depth

    within the body. Link budget analysis has shown that

    even under the worst case scenario data rates of up to

    51.43kbits/sec can be achieved over a 25kHz channel.

    I - INTRODUCTIONhe design of implanted antennas has received

    considerable attention from the research community.

    The design of these antennas is quite challenging,

    as there is a limit on the amount on power that can

    be transmitted as well as on the size of these devices. The

    limitation on the transmit power is due to the amount of

    battery power available as well as due to concerns about

    exposure to electromagnetic radiation.

    A number of different antenna designs have been

    considered for medical implants [1]-[4]. In [2] spiral and

    serpentine antenna designs have been considered and the

    authors have simulated the performance of these antennasusing a single block of muscle and a realistic human

    shoulder. The results are also verified experimentally

    using a tissue simulant material composed of TX-151,

    sugar, salt and water. A similar analysis is performed in

    [3] for spiral and planar inverted-F (PIFA) antenna.

    However, the authors have primarily focused on the human

    brain using a six-layer model (brain, CSF, Dura, bone, fat

    and skin). In both these papers the authors have considered

    a frequency of 402-405 MHz that has been recommended

    by the European Radio Communications Committee (ERC)

    for ultra-low-power, active, medical implants.

    II ANTENNA DESIGNAt 402MHz the wavelength of an electromagnetic wave

    is about 0.75m. It is obvious that any antenna with dimensions

    comparable to this wavelength cannot be used for an implant.

    The technique usually used to overcome this problem is todesign a conducting surface that is spiraled along the surface

    of the substrate. The resonant frequency of the microstrip is

    then proportional to the total length of the spiral and not to

    the length of any individual element. Although this results

    in a size reduction but its still not quite suitable for an implant

    (see table 2). We have investigated the idea of using a

    rectangular patch antenna designed to operate at millimeter

    wave frequencies ( l

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    we have considered.

    III - SIMULATION RESULTSThe antenna is placed within a three-layer body consisting

    of skin, fat and air and energized by a waveguide port

    with a normalized power of 1WF . We used air as the

    cavity around the antenna; however, in practice, someother non-conducting medium might be used.

    Fig 1. Patch implanted inside the model

    (4mm Skin, 4mm Fat, 1mm cavity).

    Tissue Permittivity Conductivity (S/m)

    5.85G Hz 31.5G Hz 5.8 5GHz 31 .5G Hz

    Skin 35.0720 14.7980 3.7602 27.9710

    Fat 4.9503 3.5970 0.2964 1.8636

    Muscle 48.4180 22.2700 5.0212 36.8130

    Table 1: Dielectric properties of human tissue at

    5.85GHz and 31.5GHz.

    (a) 31.5GHz Design (er =2.94,tand=0.0012 )

    For an isotropic radiator with a transmit power of 1W the

    power density at a distance of 1m is

    and for the embedded patch with a gain of -46.5dB the

    power density would be reduced to

    which is equal to the result obtained through p-field

    simulation (Fig 4). Now if the effective area Ae of the

    antenna is known then the received power Prat a particular

    distance can be easily calculated. The effective area [7]

    of a half wave dipole is given as

    where Gris the receive antenna gain. This gives a received

    power of -106.95dBW or -76.95dBm.

    In the absence of the body the antenna has a power density

    of -3.63dBW/m2

    at a distance of 1m. Therefore there is

    a power loss of 53.87dB within the body. Similar results

    are obtained for the reverse link using ray-tracing where

    a 52.40dB loss is observed within the layers of skin and

    fat (Fig 3). However, it must be noted that, the wireless

    communication channel between an implant and an external

    device is not symmetric and the link budget in one direction

    might be quite different from that in the other direction.

    Fig 2. Return loss of the antenna with and without the

    body.

    Fig 3. Relative Electric field strength 20log10 (/E10lEol) .

    External device to implant communication.

    Fig 5. P-field at 5.85GHz (a) H-plane (b) E-plane.

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    TECHNOLOGY FORCES (Technol. forces): Journal of Engineering and Sciences January-June 2010

    Fig 5. P-field at 5.85GHz (a) H-plane (b) E-plane.

    (b) 5.85 GHz Design ( er =80.0,tand=8.6x10-4

    )

    We next investigated the idea of using a super high

    permittivity (SHP) substrate that reduces the size of the

    patch at the expense of radiation efficiency. The material

    that we have used is ADT80 which was originally

    fabricated for hyperthermia applications [9]. It was found

    that with this substrate the patch dimensions at a frequency

    of 5.85GHz would be quite comparable to that of the

    31.5GHz antenna with RT6002 as the substrate. Simulation

    results have shown that there are two basic drawbacks of

    using this technique.

    1. The patch has very low radiation efficiency (13.96%).

    2. The patch has low directivity (2.01dBi).

    Furthermore when implanted within the body the patch

    does not have a p-field maximum along the broadside.

    However, as expected, there is lesser attenuation within

    the body (10.50dB).

    It is observed that there is a gain of 25.10dB over the

    31.5GHz patch antenna in the forward direction. The

    embedded patch has a return loss of more than 15dB and

    experiences a frequency detuning of less than 1%. Thereceived power for a half wave dipole is 67.18dBW - .

    IV-LINK BUDGET ANALYSISLet us consider the worst case scenario where the signal

    power is -76.90dBm. We keep an additional 10dB fade

    margin (ITU-R recommendations) giving us an average

    received power of -86.90dBm. The noise power can be

    calculated as

    N = kTB (5)

    where k is the Boltzman constant, T is the equivalent

    noise temperature in degree Kelvin and B is the bandwidthin Hz. At a standard room temperature of 20C the noise

    power for a 25kHz channel is calculated as -129.95dBm.

    According to ITU-R recommendations a 20dB margin is

    added to account for other sources of interference resulting

    in a noise floor of -109.95dBm. This gives us a signal to

    noise ratio of approximately 23dB. If we take the SAR

    requirements into consideration then the signal to noise

    ratio is reduced to about 5dB.

    We can now calculate the capacity of the 25kHz channel as

    C = Blog2 (1=SNR) (6)

    This gives us a theoretical maximum data rate of

    51.43kbits/sec. It seems that this should be sufficient for

    most telemetering applications like exercise EEG diagnosis

    which requires 40kbps (4k sample rate and 10 bits

    resolution). It is quite obvious that any additional

    data sources can be accommodated by increasing the

    bandwidth of the channel or by improving the SNR.

    V - CONCLUSIONThe 31.5GHz patch design is quite attractive in terms of

    its size and radiation characteristics. However, the high

    attenuation loss within the body reduces the link budgetand makes it unsuitable for deep tissue implants. The link

    budget can be greatly improved by using an SHP substrate.

    This improvement can result in greater data bandwidth

    or higher penetration depth within the body. It can also

    be used to reduce the transmit power to extremely low

    levels thus satisfying the most stringent SAR requirements.

    Finally, it must be noted that the return loss of the antenna

    increases inside the body and there is also some frequency

    detuning. Higher return loss is a desirable characteristic

    but frequency detuning is not and can be removed by

    adjusting the dimensions of the antenna such that the null

    occurs at the desired frequency.

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    REFERENCES

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    f For the 10gm tissue that we have used the transmit power

    should be less than 16mW (1.6W/kg x0.010kg). This wouldreduce our link budget by approximately 18dB.

    The formula given in the text uses directivity instead of

    gain;

    however, this is only valid if there is no loss in radiation.

    CST (Computer Simulation Technology) considers the

    antenna and

    the body as the radiator. Therefore, the gain is the gain of

    the complete

    structure and not just the designed antenna.

    Table 2. Comparison of six different antennas designed for medical implants. The size of our antenna is

    governed by the dimensions of the ground plane.