klumperink-ucd-highly linear mixer-first receivers and n

Eric Klumperink – UCD 12 Aug 2019: High Linearity N-path Filters & Mixers

Highly Linear Mixer-First Receivers and N-path Filters

Eric Klumperink

University of Twente, Enschede, The Netherlands


Outline

• Introduction• N-path Filter basics• Gm-Assisted & Gain-Boosted N-Path filters• Higher order Passive Filters• Exploit Positive Capacitive-Feedback• Adding Transmission zero’s• Exploit Implicit Capacitive Stacking• Conclusion

2


Flexible RF Filtering wanted!

• Armstrong 1915 .. to • Trend Analog Digital• ADC feasibility & power:

– RF-filtering– Mix down

• Integration in CMOS• Inductors:

– Large area, poor Q– Limited tuning-range

• Challenges:– Selectivity high Q– Linearity passive R, L, C– Digitally Programmable– “SAW-less” CMOS receivers

ADC DSPRF

3


Example of a SAW-less diversity receiver

Wanted:• High Selectivity• High linearity• Tunable fcenter

Concepts that fit:• N‐path filters• Mixer‐first RX

4


RC>>Ton

Ton = ¼ period

Clocks: fswitch1234

fsine fswitch

Pass/Stop depends on fsine

“Pass”

Basic N-Path Filter Concept (N=4)

5


RC>>Ton

fsine =1.5 fswitch

Ton = ¼ period

Clocks: fswitch1234

RC>>Ton

fsine fswitch

Pass/Stop depends on fsine

“Pass”

“Stop”

Basic N-Path Filter Concept (N=4)

6


Equivalent R-L-C filter model

0 0.5 1 1.5 2 2.5 3 3.5 4-50

-40

-30

-20

-10

0

Example: differential input4‐path filter @fs=0.5GHz:

[GhaffariJSSC11] [IzukaTCAS16][PavanTCAS17]

If ffs then:

))/2cos(1(2))/2cos(1(

22

2

NNRNNRP

CR

RRNC

p

pp 2

)(

psp Cf

L 2)2(1

Note: extra harmonic responses

N-path filter

7


High Q high selectivityQuality factor is high (>>10)!

Q= 2 RC N fclock

BWfQ clock

GHz

MHz

Low pass – Bandpass transformation

RC21BW

RCN21BW

clockf

Shift & shrink by N

8


Not a new idea ...

• Down-convert + LPF + Upconvert = BPF

[Barber, Wireless Engineer, May 1947]


Band-Pass Filter (BPF)

Band-Reject Filter (BRF)

“Commutated Networks”

[Smith1953][LePage1953]

10


ISSCC 1960: Go solid-state!!

[FranksISSCC60]

11


ISSCC 1960 Notch filter

High Q !

KC = 1000Cycles/sec

now CMOS is10.000 x faster

12


8-path Notch-Filter

0 200 400 600 800 1000 1200 1400-30

-20

-10

0

Frequency [MHz]

S 21 [d

B]

S S OUT

L

P

P

P

[Ghaffari, ISSCC2012; JSSC2013]

Flexible NotchUp to ~1.2GHz

13


4-Path band-pass filter

[GhaffariRFIC2010,GhaffariJSSC11]

* Theory: ~1dB; meas. setup dominates

Flexibly programmable & Interference robust

~3dB loss@ 1GHz(65nm)

14


Balanced

090180

0I+

I-

Q+

Q-

I/Q image rejection

-0.9dB conversion gain 0.9dB NF

Need Mixing? Use BB Capacitor-voltages

onTRC [CookJSSC06][SoerISSCC09]

25%

270

270

90

180R C

C

C

C

15


Need Z-match? Add RB (or other loss)

[AndrewsJSSC10] [YangTCAS14]

𝑍 𝑅 𝑅 𝑍

𝑠𝑖𝑛𝑐

𝑁𝑁

[IzukaTCAS16] [PavanTCAS17]

16


2

Lower-Noise Z-match? Shunt-feedback

[AndrewsJSSC10]

17

Input noise current variance 1/RfbRBaseband = Rfb/(1+Av)


Speed limitation? fT matters

• Cut-off frequency limited by MOS-switch parasitics:

• Charge sharing between CL via Cin,total

• Rough model: switched-capacitor resistor to ground (Loss)• Detailed model and analysis of series-inductance benefit:

18

𝐶𝑠𝑏

𝐶𝑔𝑠

𝑓 , 1

𝑅 , 𝐶 ,

𝑓 𝑁 1

[PavanTCAS18-1]S. Pavan, E.A.M.Klumperink, "Analysis of the Effect of Source Capacitance and Inductance on N-Path Mixers and Filters”, TCAS-I, 2017

[YangTCAS15]𝐶𝑖𝑛, 𝑡𝑜𝑡𝑎𝑙


Performance Limitations

• LO Phase Noise:– essentially an N-path filter is a set of mixers...– so: reciprocal mixing with phase noise is an issue

• Harmonic responses• Folding

19


Outline

• Introduction• N-path Filter basics• Gm-Assisted & Gain-Boosted N-Path filters• Higher order Passive Filters• Exploit Positive Capacitive-Feedback• Adding Transmission zero’s• Exploit Implicit Capacitive Stacking• Conclusion

20


x N

Ro

Gm Rfvin

vinvout

vout x N

a) Increase R-level > 50e.g. Ro = 500 C/10

b) Notch in feedback BPFMiller effect “Gain Boosted”

Gm-Assisted lower power: Increase Z-level!!

• ..MHz-BW @50ohm big C, Rsw<<50 & high LO-power• Solution: higher Z-level!

Gm

Ro

[BorremansJSSC2011] [Liempd,JSSC2014][SoerISSCC2014]

[Lin/MakJSSC2014]; [LinISSCC2015] [LinTCAS1-2014][ParkISSCC/JSSC2014]

21


Filter Shape and Stop-Band Rejection

Desired: low loss, flat in-band shape, sufficient Roll-off(more than “just a single real pole”)

Q : Component Quality Factor

Courtesy Pingyue Song & Hossein Hashemi [SongISSCC18]

22


High-order N-path BPFs

• Use N-path filter as parallel LC tank• Synthesize a high-order BPF with gyrator coupling• All-pole singly-terminated 6th-order BPF

Isolate the “resonators”by Gm (Inverters)

[DarvishiJSSC13]

23


Linearity and NF

[DarvishiJSSC13]

24


Linearity Limitation

RF

/

[Darvishi, ISSCC2013]

Active circuitlimiting the linearity!

25


Outline

• Introduction• N-path Filter basics• Gm-Assisted & Gain-Boosted N-Path filters• Higher order Passive Filters• Exploit Positive Capacitive-Feedback• Adding Transmission zero’s• Exploit Passive Gain• Conclusion

26


Extra filter roll-off by Passive IIR-filtering

27

[XuJSSC16]


Passive RX N-Path BPF & Mixer architecture

• Passive early BPF for high linearity• V-I, mix & differential current subtraction

Mixer

Quadraturemixingoff-chip

[LienISSCC2017]

28


• LC tanks act as ‘’open’’

Current Path for In-band signals

29


• LC tanks act as ‘’short’’ • Blocker current circulates in R-network

for Out-of-band (OOB) signals

Mixer

30

[LienISSCC2017]


Differential Implementation with shared switch

• Switch is shared and RSW is reduced to half• Improves linearity for both in-band and OOB

RF+

RF─

Mixer switches(large W/L)

Set DC(small W/L)

VirtualGND


High Linearity “Bottom-Plate Mixing”

Top-plate mixing

Bottom-plate mixing

In-band+6dB

+10dB

• BW of BPF=30MHz• Same W/L for NMOS switches• PSP MOS transistor model• 1GHz fLO• Two-tone test: f1=fLO-∆f f2=fLO-2∆f+500kHz

32


Measured gain and S11S 1

1

─33dB/dec ─32dB/dec

28nm bulk-CMOS

33


Outline

• Introduction• N-path Filter basics• Gm-Assisted & Gain-Boosted N-Path filters• Exploit Positive Capacitive-Feedback• Higher order Passive Filters• Adding Transmission zero’s• Exploit Implicit Capacitive Stacking• Conclusion

34


Synthesize complex poles via feedback

Add positive feedback C2

complex poles !

while also:Low Noise

High Linearity

negative feedback C1+

Note: output impedance: ro // Co

Aa<1

35


Outline


36


Even more roll-off needed? Add TZs

• Increase filter slope adding transmission zeros (TZs):


37


Implementation Problem: Charge Sharing


38


Transmission zeros in gain boosted N-path filter

• Notch by CSE in FB(s) Overall Band-pass transfer• Add CSH: introduces notches in the transfer

39

[QiJSSC18][LuoMTT16]

Notches Transmission zero (albeit less close to the pass-band)

=0 if:


Outline


40


RFIC 2019 - MO2B-4

A Sub-mW All-Passive RF Front End with Implicit Capacitive Stacking Achieving 13 dB

Gain, 5 dB NF and +25 dBm OOB-IIP3Vijaya Kumar Purushothaman, Eric Klumperink,

Berta Trullas Clavera, and Bram NautaIC Design group

University of Twente, Enschede, The Netherlands

41[PurushothomanRFIC19]


Typical performance N-path front-ends

42


Objective: bring power dissipation down

43

Large power consumptionClock-generation & LO drivers• Large switches High linearity• Low phase noise Reciprocal

mixing

Low-power Mixer-first RX with similar performance


Existing technique

44

[Lien, ISSCC 2017]

Single-ended(Ideal switch)

-

+VIN

Rs

Rs

VA+

VA-

Read-out from the top-plate of C

Φ0

C

Φ90

C

Φ180

C

Φ270

CVIN

Rs

VA


Proposed technique - 1

45

Capacitive stacking 6 dB Conversion gain (V-V)

Read-out from the bottom-plate of C

[Lien, ISSCC 2017]

VINRs

Φ90

CVA1 VA2

Φ0

C

Φ270

CVA3 VA4

Φ180

C

Φ0

C

Φ90

C

Φ180

C

Φ270

CVIN

Rs

VA


Voltage at the top-plate of the Capacitor

46

RC >> Ton

fin ≈ 1.0 x fLO

VINR

Φ90 C

Φ0 C

Φ270 C

Φ180 C

VRF

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

For ideal switches same as for top-plate mixing


Voltage at the bottom-plate of the Capacitor

47

RC >> Ton

fin ≈ 1.0 x fLO

VRF

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

VINR

Φ90 C

Φ0 C

Φ270 C

Φ180 CVA1

VA1

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270


Bottom-plate read out

48

Φ0 Φ90 Φ180 Φ270

RC >> Ton

fin ≈ 1.0 x fLO VB180

CB

Φ180 VA1

VINR

Φ90 C

Φ0 C

Φ270 C

Φ180 CVA1

VRF

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

VA1

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

Read out VA1 on capacitor CB during 180


Bottom-plate read out – Capacitive stacking

49

RC >> Ton

“Implicit Capacitive stacking”(no extra switches, just re-use existing ones)Doubled voltage referred to ground!

fin ≈ 1.0 x fLO

VINR

Φ90 C

Φ0 C

Φ270 C

Φ180 CVA1

+- +

- VB180

CB

Φ180 VA1

VRF

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

VA1

Φ0 Φ90 Φ180 Φ270 Φ0 Φ90 Φ180 Φ270

Φ0 Φ90 Φ180 Φ270


Summary

50

Compared to Top-plate mixer with same ‘C’• 6 dB more In-band V-V gain • Lower bandwidth

Additional 6dB conversion gainrelaxes baseband LNA design


Out-of-band linearity–Passive mixer-first RX

51

CVINR LO

Simplified equivalent model

[Yang, TCAS2015]

𝐎𝐎𝐁 𝐈𝐈𝐏𝟑 ∝𝐑

𝐑𝐒𝐖

𝟑

ZCTVINR Rsw

Low Rsw Large Cgs Power

E.g. [Lien, ISSCC2017]

Rsw = 2 ohm OOB-IIP3 = +44 dBmClock power = 30 mW / GHz


Impedance up-conversion

52

CVINR LO

CVINR

1:N

NVINN2R RswZCT

Source impedance, R N2R

• High OOB linearity • Low-power clock drivers • Extra V-V conversion gain


Implementation – Top level

53

Process: GF22nm FDSOITransformer: Off-chipTurn ratio: 1:2

Clock-divider + buffer – Only power consuming blocks

NMOS Switches - 9.6um/20nm

RF capacitors (CR1 – CR8)• 6.4 pF for 50 ohm matching at 1 GHz

BB capacitors (CB1-CB4)• 4 pF Bandwidth = 15 MHzCB2

N2 N8

Φ2 Φ4 BBQ+

CB3

N3 N5

Φ3 Φ1 BBI-

Φ1 Φ2 Φ3 Φ4

2LO+

2LO- ÷2

Φ4

N4

N8

CR4

CR8

Φ3

N3

N7

CR3

CR7

Φ2

N2

N6

CR2

CR6

Φ1 N1

N5

CR1

CR5

VRF

Rs c

RF-

RF+

On-chip

CB1

N1 N7

Φ1 Φ3 BBI+

1:N

CB4

N4 N6

Φ4 Φ2 BBQ-


Conversion gain and S11 vs LO

54

fLO : 0.6 – 1.3 GHzV-V Gain: 10 – 15 dB

Degrades at high fLO :

• Parasitic capacitance at RF terminals

• Limited bandwidth of Transformers


Gain and Noise figure vs IF

55

Features ResultsV-V Gain ~14 dB

IF BW-3dB 16 MHz

DSB NF 5 – 6 dB

Power 0.6 mW

At fLO = 1 GHz


Linearity and blocker tolerance

56

Features ResultsOOB – IIP3 +25 dBm

OOB – IIP2 +66 dBm

B1dB 0 dBm

Δf = 10 x IF-BW3-dB


Comparison (High-performance mixer-first RX)

57

Features AndrewsJSSC10

NejdelRFIC15

LinISSCC15

WesterveldRFIC16

LienRFIC17

This Work

Technology (nm) 65 65 65 65 45 SOI 22 FDSOI

Frequency (GHz) 0.1 – 2.4 2 – 3 0.1 - 1.5 0.03 – 0.3 0.2 - 8 0.6 – 1.3

Power (mW) 37-70 27-75 11 @ 1.5 G 21-36 50 + 30 / 1G 0.6 @ 1G

Gain/BW (dB/MHz) 40-70 / 10 7.5 / 3 38 / 2 21-36 / 2-40 21 / 10 13 - 14 / 16

DSB NF (dB) 3 - 5 2.5 - 4.5 2.9 6 2.3 - 5.4 5 – 6

IIP3 (dBm@∆f/BW ) 25 @ 10 26 @ 10 13 @15 41 @ 20 39 @ 8 25 @ 10

IIP2 (dBm@∆f/BW ) 56 @ 10 65 @ 10 47 @ 15 90 @ 20 88 @ 8 66 @ 10

LO leakage (dBm) -65 -60 N.A. N.A. -65 < -70

Active Area (mm2) 0.75 0.23 0.028* 0.8* 0.8* 0.23

* Total area


Comparison (Low power RF front-end)

58

Features Bryant RFIC12

LinISSCC14

SelvakumarJSSC15

LeeTMTT18

Krishnamurthy ESSCIRC18

This Work

Technology (nm) 65 65 130 28 28 22 FDSOI

Frequency (GHz) 2.45 0.43 – 0.96 2.4 2.4 2.4 0.6 – 1.3

Power (mW) 0.4 1.15 0.6 0.64 0.58 0.6 @ 1G

Gain/BW (dB/MHz) 27.5 / NA 50 / NA 55.5 / 2 50 / 1 19 / 3.6 13 - 14 / 16

DSB NF (dB) 9 8.1 15.1 6.5 11.9 5 - 6

IIP3 (dBm@∆f/BW ) -21 @ NA -20.5 @ NA

-15.8 @ 2.5 0.9 @ 10 3.3 @ 13.9 25 @ 10

Blocker NF (dB / dBm @ MHz)

NA 13.7 / -20 @ 50

NA NA NA 10 / -15 @ 80

Active Area (mm2) 0.08 0.2* 0.25 0.25 NA 0.23

Matching network LC Q=5 None LC LC Q=50 XFMR 1:4 XFMR 1:2

* Total area


Conclusions RFIC’19 Paper

• Novel fully-passive bottom-plate mixer with differential readout– Capacitive stacking passive 6 dB voltage gain

• Impedance up-conversion via transformer– Large OOB IIP3 performance with smaller switches– Voltage amplification combined with impedance match

• A sub-mW 1-GHz RF front-end with 14 dB gain, NF < 6 dB, and +25 dBm OOB-IIP3

59


Overall Conclusions

• N-path filter and mixers allow for high-Q, high-linearity receivers with a digitally programmable center-frequency

• N-path Filter suppression and shape can be improved by:– Higher order filter via Transconductor/Gyrator coupling– Gain-Boosting– Adding extra switched-capacitor IIR-filtering– Exploit positive capacitive feedback– Adding transmission zeros

• Low-power variants are possible exploiting:– Gain-boosted techniques– Exploit implicit capacitor stacking and passive gain

60


IIP3 versus normalized offset-frequency

Note: RF-3dB BW = Equivalent RF-referred (double side-band) -3dB bandwidth


B1dB vs. normalized offset-frequency

Note: RF-3dB BW = Equivalent RF-referred (double side-band) -3dB bandwidth


• [AndrewsJSSC10] C. Andrews and A. C. Molnar, "A Passive Mixer-First Receiver With Digitally Controlled and Widely TunableRF Interface," IEEE JSSC, pp. 2696-2708, 2010.

• [Barber1947] N. F. Barber, "Narrow Band-Pass Filter Using Modulation," Wireless Engineer, pp. 132-134, 1947.• [CookJSSC06] B.Cook, A.Berny, A.Molnar, S.Lanzisera, K.Pister, “Low-power 2.4-GHz transceiver with passive RX front-end

and 400-mV supply”, IEEE JSSC, pp. 2757–2766, Dec. 2006.• [DarvishiJSSC13] M.Darvishi, R. van der Zee, B.Nauta, "Design of Active N-Path Filters," IEEE JSSC, pp.2962-2976, Dec.2013.• [FranksISSCC60] L. Franks and I. Sandberg, “An alternative approach to the realizations of network functions: The N-path filters,”

Bell Syst. Tech. J., pp. 1321–1350, Sep. 1960.• [GhaffariJSSC11] A. Ghaffari, E. Klumperink, M. Soer, and B. Nauta, “Tunable high-Q N-path band-pass filters: Modeling and

verification,” IEEE JSSC, pp. 998–1010, May 2011.• [GhaffariJSSC13] A. Ghaffari, E.A.M. Klumperink, B. Nauta, "Tunable N-Path Notch Filters for Blocker Suppression: Modeling

and Verification," IEEE JSSC, vol.48, no.6, pp.1370,1382, June 2013• [HedayatiJSSC15] H. Hedayati, W. F. A. Lau, N. Kim, V. Aparin, and K. Entesari, "A 1.8 dB NF Blocker-Filtering Noise-Canceling

Wideband Receiver With Shared TIA in 40 nm CMOS," IEEE JSSC, vol. 50, pp. 1148-1164, 2015.• [HedayatiVLSI14] [Hedayati, V. Aparin, and K. Entesari, "A +22dBm IIP3 and 3.5dB NF wideband receiver with RF and

baseband blocker filtering techniques," in 2014 Symposium on VLSI Circuits Digest of Technical Papers, 2014, pp. 1-2.• [IzukaTCAS16] T. Iizuka and A. A. Abidi, "FET-R-C Circuits: A Unified Treatment - Part I: Signal Transfer Characteristics of a

Single-Path," IEEE Transactions on Circuits and Systems I: Regular Papers, vol. 63, pp. 1325-1336, 2016; Part II: Extension toMulti-Paths, Noise Figure, and Driving-Point Impedance,”,--, vol. 63, pp. 1337-1348, 2016.

• [LePage1953] W. R. LePage, C. R. Cahn, and J. S. Brown, "Analysis of a comb filter using synchronously commutatedcapacitors," American Institute of Electrical Engineers, Part I: Communication and Electronics, Tr. of the, vol. 72, pp. 63-68, 1953.

• [LuoMTT16] C. k. Luo, P. S. Gudem, and J. F. Buckwalter, "A 0.4 - 6-GHz 17-dBm B1dB 36-dBm IIP3 Channel-Selecting Low-Noise Amplifier for SAW-Less 3G/4G FDD Diversity Receivers," IEEE MTT, vol. 64, no. 4, pp. 1110-1121, 2016.

• [LinTCAS14] Zhicheng Lin; Pui-In Mak; Martins, R.P., "Analysis and Modeling of a Gain-Boosted N-Path Switched-CapacitorBandpass Filter,“, IEEE TCAS-I, vol.61-9, pp.2560,2568, Sept. 2014

• [LinISSCC15] Zhicheng Lin; P.-I. Mak; R.P. Martins, "2.4 A 0.028mm2 11mW single-mixing blocker-tolerant receiver with double-RF N-path filtering, S11 centering, +13dBm OB-IIP3 and 1.5-to-2.9dB NF" ISSCC, 22-26 Feb. 2015.

References

63


• [LienISSCC17] Y. Lien, E. Klumperink, B. Tenbroek, J. Strange, and B. Nauta, "A high-linearity CMOS receiver achieving+44dBm IIP3 and +13dBm B1dB for SAW-less LTE radio," ISSCC, pp. 412-413 , 2017.

• [LienJSSC18] Y. C. Lien, E. A. M. Klumperink, B. Tenbroek, J. Strange, and B. Nauta, "Enhanced-Selectivity High-Linearity Low-Noise Mixer-First Receiver With Complex Pole Pair Due to Capacitive Positive Feedback," IEEE Journal of Solid-State Circuits,vol. PP, no. 99, pp. 1-13, 2018.

• [MirzaeiTCAS11] A. Mirzaei, H. Darabi, "Analysis of Imperfections on Performance of 4-Phase Passive-Mixer-Based High-QBandpass Filters in SAW-Less Receivers," IEEE TCAS-I, pp.879,892, May 2011.

• [PavanTCAS17-1] S. Pavan, E.A.M.Klumperink, "Simplified Unified Analysis of Switched-RC Passive Mixers, Samplers, and N -Path Filters Using the Adjoint Network, IEEE TCAS-I, Vol.64, Issue 10, pp. 2714-2725, 2017.

• [PavanTCAS18-1] S. Pavan, E.A.M.Klumperink, "Analysis of the Effect of Source Capacitance and Inductance on N-Path Mixersand Filters, IEEE TCAS-I, vol. 65, no. 5, pp. 1469-1480, May 2018..

• [PavanTCAS18-2] S. Pavan, E.A.M.Klumperink, “Generalized Analysis or Higher Order N-Path Mixer and Filters using the AdjointNetwork”, accepted for IEEE TCAS-I, 2018 (prepublication doi: 10.1109/TCSI.2018.2816342) .

• [PurushothomanRFIC19] Vijaya Kumar Purushothaman, Eric Klumperink, Berta Trullas Clavera, Bram Nauta, "A Sub-mW All-Passive RF Front End with Implicit Capacitive Stacking Achieving 13 dB Gain, 5 dB NF and +25 dBm OOB-IIP3“, RadioFrequency Integrated Circuits Symposium (RFIC), 2019.

• [QiJSSC18] G. Qi, B. van Liempd, P. I. Mak, R. P. Martins and J. Craninckx, "A SAW-Less Tunable RF Front End for FDD andIBFD Combining an Electrical-Balance Duplexer and a Switched-LC N-Path LNA," IEEE JSSC,doi: 10.1109/JSSC.2018.2791477

• [Smith1953] B. D. Smith, "Analysis of Commutated Networks," Aeronautical and Navigational Electronics, Transactions of the IREProfessional Group on IRE Trans., vol. PGAE-10, pp. 21-26, December 1953.

• [SoerISSCC09] M.C.M.Soer, E.A.M.Klumperink, Z.Ru, F.E.van Vliet, B.Nauta,"A 0.2-to-2.0GHz 65nm CMOS Receiver WithoutLNA Achieving >11dBm IIP3 and <6.5dB NF," ISSCC, pp.222-223, Feb. 2009.

• [SoerTCAS10] M.C.M.Soer, E.A.M.Klumperink, P.T. de Boer, F.E.van Vliet, B.Nauta, "Unified Frequency-Domain Analysis ofSwitched-Series-RC Passive Mixers and Samplers," IEEE TCAS-I, pp. 2618-2631, 2010.

• [SongISSCC2018] Pingyue Song, Hossein Hashemi, “A 13th-Order CMOS Reconfigurable RF BPF with Adjustable TransmissionZeros for SAW-Less SDR Receivers”, ISSCC, pp.416-418, Feb. 2018.

• [XuJSSC16] Y. Xu and P. R. Kinget, "A Switched-Capacitor RF Front End With Embedded Programmable High-Order Filtering,"IEEE Journal of Solid-State Circuits, vol. 51, no. 5, pp. 1154-1167, 2016.

• [WesterveldRFIC16] H. Westerveld, E.A.M. Klumperink, B. Nauta, "A cross-coupled switch-RC mixer-first technique achieving+41dBm out-of-band IIP3“, Radio Frequency Integrated Circuits Symposium (RFIC) pp. 246-249, 2016.

• [YangTCAS2015] D. Yang, C. Andrews, and A. Molnar, "Optimized Design of N-Phase Passive Mixer-First Receivers inWideband Operation," IEEE Transactions on Circuits and Systems I: Regular Papers, vol. 62, no. 11, pp. 2759-2770, 2015.

References

64

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klumperink-ucd-highly linear mixer-first receivers and n