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n 0.5Msps to 20Msps sampling frequencyn Adaptive power consumption: 120mW @
20Msps, 95mW@10Mspsn Single supply voltage: 2.5V
Independent supply for CMOS output stage with 2.5V/3.3V capability
n ENOB=11.2 @ Nyquistn SFDR= -81.5 dBc @ Nyquistn 1GHz analog bandwidth Track-and-Holdn Common clocking between channelsn Dual simultaneous Sample and Hold inputsn Multiplexed outputsn Built-in reference voltage with external bias
capability.
DESCRIPTIONThe TSA1204 is a new generation of high speed,dual-channel Analog to Digital converter pro-cessed in a mainstream 0.25m CMOS technolo-gy yielding high performances and very low powerconsumption.The TSA1204 is specifically designed for applica-tions requiring very low noise floor, high SFDRand good isolation between channels. It is basedon a pipeline structure and digital error correctionto provide excellent static linearity and over 11.2effective bits at Fs=20Msps, and Fin=10MHz.For each channel, a voltage reference is integrat-ed to simplify the design and minimize externalcomponents. It is nevertheless possible to use thecircuit with external references. Each ADC outputs are multiplexed in a commonbus with small number of pins. A tri-state capabili-ty is available for the outputs, allowing chip selec-tion. The inputs of the ADC must be differentiallydriven. The TSA1204 is available in extended (-40 to+85C) temperature range, in a small 48 pinsTQFP package.APPLICATIONSn Medical imaging and ultrasoundn 3G base stationn I/Q signal processing applicationsn High speed data acquisition systemn Portable instrumentationORDER CODE
PIN CONNECTIONS (top view)
BLOCK DIAGRAM
PACKAGE
Part Number Temperature Range Package Conditioning Marking
TSA1204IF -40C to +85C TQFP48 Tray SA1204ITSA1204IFT -40C to +85C TQFP48 Tape & Reel SA1204IEVAL1204/BA Evaluation board
SELECT
CLK
DGN
D
REFPQ
AGND
AVCC
DGN
D
DVCC
DVCC
INCMQ
REFM
Q
GN
DBI
D5
D6
D7
D8
D9
D10
D11(MSB)
AVCCB
indexcorner
1
23
4
5
6
7
8
9
10
11
32
31
30
29
28
2726
13 14 15 16 17 18 19 20 21 22
47
25
33
12
23 24
35
34
36
48 44 43 42 41 40 39 38 3746 45
TSA1204
VCCBE
GNDBE
AGND
INI
AGND
AGND
IPOL
AGND
AGND
INBQ
INIB
AGND
INQ
D2
D3
REFM
I
D0(LSB)
OEB
AVCC
REFPI
INCMI
AVCC
VCCBI
GNDBE
VCCBI D1
VCCBE
D4
Timing
BuffersIPOL
CLK+2.5V/3.3V
VINI
VINBI
OEB
VINCMI
GND
VINQ
VINBQ
VINCMQ
AD 12I channel
AD 12Q channel
12
12 12
12
MUX
REF I
REF Q
SELECT
VREFPI
VREFPQ
Polar.
VREFMI
VREFMQ
common mode
common mode
D0TOD11
VCCBE
GNDBE
7 7 mm TQFP48
TSA1204
DUAL-CHANNEL, 12-BIT, 20MSPS, 120mW A/D CONVERTER
February 2003
TSA1204
2/20
CONDITIONSAVCC = DVCC = VCCB = 2.5V, Fs= 20Msps, Fin=10.5MHz, Vin@ -1dBFS, VREFP=1.0V, VREFM=0VTamb = 25C (unless otherwise specified)DYNAMIC CHARACTERISTICS
TIMING CHARACTERISTICS
Symbol Parameter Test conditions Min Typ Max Unit
SFDR Spurious Free Dynamic Range -81.5 -71.0 dBcSNR Signal to Noise Ratio 66.9 68.5 dBTHD Total Harmonics Distortion -80 -70 dBc
SINAD Signal to Noise and Distortion Ratio 64.8 68 dBENOB Effective Number of Bits 10.6 11.2 bits
Symbol Parameter Test conditions Min Typ Max Unit
FS Sampling Frequency 0.5 20 MHzDC Clock Duty Cycle 45 50 55 %TC1 Clock pulse width (high) 22.5 25 nsTC2 Clock pulse width (low) 22.5 25 nsTod Data Output Delay (Clock edge to Data Valid) 10pF load capacitance 9 ns
Tpd I Data Pipeline delay for I channel 7 cycles
Tpd Q Data Pipeline delay for Q channel 7.5 cyclesTon Falling edge of OEB to digital output valid data 1 nsToff Rising edge of OEB to digital output tri-state 1 ns
TSA1204
3/20
TIMING DIAGRAM
PIN CONNECTIONS (top view)
N-1N
N+1
N+6
N+7N+2
N+5N+3
N+4
N+8
CLK
Tpd I + Tod
N+9N+10
N+11
N+12N+13
DATAOUTPUT
sample N+1I channel
sample NQ channel
sample N+1Q channel
sample N+2I channel
sample N+2Q channel
sample N+3I channel
OEB
Simultaneous sampling on I/Q channels
SELECT
sample N-9I channel
sample N-8I channel
sample N-7Q channel
sample N-6Q channel
CLOCK AND SELECT CONNECTED TOGETHER
Tod
I
Q
SELECT
CLK
DGN
D
REFPQ
AGND
AVCC
DGND
DVCC
DVCC
INCMQ
REFMQ
GNDBI
D5
D6
D7
D8
D9
D10
D11(MSB)
AVCCB
indexcorner
1
23
4
5
6
7
8
9
10
11
32
31
30
29
28
27
26
13 14 15 16 17 18 19 20 21 22
47
25
33
12
23 24
35
34
36
48 44 43 42 41 40 39 38 3746 45
TSA1204
VCCBE
GNDBE
AGND
INI
AGND
AGND
IPOL
AGND
AGND
INBQ
INIB
AGND
INQ
D2
D3
REFMI
D0(LSB)
OEB
AVCC
REFPI
INCM
I
AVCC
VCCBI
GNDBE
VCCBI D1
VCCBE
D4
TSA1204
4/20
PIN DESCRIPTION
ABSOLUTE MAXIMUM RATINGS
OPERATING CONDITIONS
Pin No Name Description Observation Pin No Name Description Observation
1 AGND Analog ground 0V 25 GNDBE Digital buffer ground 0V2 INI I channel analog input 26 VCCBE Digital Buffer power supply 2.5V/3.3V3 AGND Analog ground 0V 27 D11(MSB) Most Significant Bit output CMOS output (2.5V/3.3V)4 INBI I channel inverted analog input 28 D10 Digital output CMOS output (2.5V/3.3V)5 AGND Analog ground 0V 29 D9 Digital output CMOS output (2.5V/3.3V)6 IPOL Analog bias current input 30 D8 Digital output CMOS output (2.5V/3.3V)7 AVCC Analog power supply 2.5V 31 D7 Digital output CMOS output (2.5V/3.3V)8 AGND Analog ground 0V 32 D6 Digital output CMOS output (2.5V/3.3V)9 INQ Q channel analog input 33 D5 Digital output CMOS output (2.5V/3.3V)10 AGND Analog ground 0V 34 D4 Digital output CMOS output (2.5V/3.3V)11 INBQ Q channel inverted analog input 35 D3 Digital output CMOS output (2.5V/3.3V)12 AGND Analog ground 0V 36 D2 Digital output CMOS output (2.5V/3.3V)13 REFPQ Q channel top reference voltage 37 D1 Digital output CMOS output (2.5V/3.3V)14 REFMQ Q channel bottom reference
voltage0V 38 D0(LSB) Least Significant Bit output CMOS output (2.5V/3.3V)
15 INCMQ Q channel input common mode 39 VCCBE Digital Buffer power supply 2.5V/3.3V - See Application Note
16 AGND Analog ground 0V 40 GNDBE Digital buffer ground 0V17 AVCC Analog power supply 2.5V 41 VCCBI Digital Buffer power supply 2.5V18 DVCC Digital power supply 2.5V 42 DVCC Digital Buffer power supply 2.5V19 DGND Digital ground 0V 43 OEB Output Enable input 2.5V/3.3V CMOS input20 CLK Clock input 2.5V CMOS input 44 AVCC Analog power supply 2.5V21 SELECT Channel selection 2.5V CMOS input 45 AVCC Analog power supply 2.5V22 DGND Digital ground 0V 46 INCMI I channel input common mode23 DVCC Digital power supply 2.5V 47 REFMI I channel bottom reference voltage 0V24 GNDBI Digital buffer ground 0V 48 REFPI I channel top reference voltage
Symbol Parameter Values UnitAVCC Analog Supply voltage 1) 0 to 3.3 VDVCC Digital Supply voltage 1) 0 to 3.3 V
VCCBE Digital buffer Supply voltage 1) 0 to 3.6 VVCCBI Digital buffer Supply voltage 1) 0 to 3.3 VIDout Digital output current -100 to 100 mATstg Storage temperature +150 C
ESDHBM: Human Body Model2)
CDM: Charged Device Model3)2
1.5kV
Latch-up Class4) A1). All voltages values, except differential voltage, are with respect to network ground terminal. The magnitude of input and output voltages must not exceed -0.3V or VCC2). ElectroStatic Discharge pulse (ESD pulse) simulating a human body discharge of 100 pF through 1.5k3). Discharge to Ground of a device that has been previously charged.4). Corporate ST Microelectronics procedure number 0018695
Symbol Parameter Min Typ Max UnitAVCC Analog Supply voltage 2.25 2.5 2.7 VDVCC Digital Supply voltage 2.25 2.5 2.7 V
VCCBE External Digital buffer Supply voltage 1.8 2.5 3.5 VVCCBI Internal Digital buffer Supply voltage 2.25 2.5 2.7 V
TSA1204
5/20
1) Condition VRefP-VRefM>0.3V
ELECTRICAL CHARACTERISTICSAVCC = DVCC = VCCB = 2.5V, Fs= 20Msps, Fin=2MHz, Vin@ -1dBFS, VREFP=1.0V, VREFM=0VTamb = 25C (unless otherwise specified)ANALOG INPUTS
DIGITAL INPUTS AND OUTPUTS
VREFPIVREFPQ Forced top voltage reference
1) 0.96 1.4 V
VREFMIVREFMQ Forced bottom reference voltage
1) 0 0.4 V
INCMIINCMQ
Forced input common mode voltage 0.2 1 V
Symbol Parameter Min Typ Max Unit
Symbol Parameter Test conditions Min Typ Max Unit
VIN-VINB Full scale reference voltage Differential inputs mandatory 1.1 2.0 2.8 VppCin Input capacitance 7.0 pFReq Equivalent input resistor 3 K
BW Analog Input Bandwidth Vin@Full Scale, Fs=20Msps 1000 MHzERB Effective Resolution Bandwidth 70 MHz
Symbol Parameter Test conditions Min Typ Max Unit
Clock and Select inputsVIL Logic "0" voltage 0 0.8 VVIH Logic "1" voltage 2.0 2.5 V
OEB input
VIL Logic "0" voltage 0 0.25 x VCCBE V
VIH Logic "1" voltage 0.75 x VCCBE VCCBE V
Digital OutputsVOL Logic "0" voltage Iol=10A 0 0.1 x VCCBE V
VOH Logic "1" voltage Ioh=10A 0.9 x VCCBE VCCBE V
IOZ High Impedance leakage current OEB set to VIH -1.7 1.7 ACL Output Load Capacitance 15 pF
TSA1204
6/20
ELECTRICAL CHARACTERISTICSAVCC = DVCC = VCCB = 2.5V, Fs= 20Msps, Fin=2MHz, Vin@ -1dBFS, VREFP=1.0V, VREFM=0VTamb = 25C (unless otherwise specified)REFERENCE VOLTAGE
POWER CONSUMPTION
ACCURACY
MATCHING BETWEEN CHANNELS
Symbol Parameter Test conditions Min Typ Max Unit
VREFPIVREFPQ
Top internal reference voltage 0.807 0.89 0.963 V
VINCMIVINCMQ
Input common mode voltage 0.40 0.46 0.52 V
Symbol Parameter Min Typ Max Unit
ICCA Analog Supply current 40 49.5 mAICCD Digital Supply Current 2 3 mA
ICCBE Digital Buffer Supply Current (10pF load) 6.2 9 mAICCBI Digital Buffer Supply Current 73 221 A
Pd Power consumption in normal operation mode 120 155 mW
Rthja Thermal resistance (TQFP48) 80 C/W
Symbol Parameter Min Typ Max Unit
OE Offset Error -1.8 -0.5 1.8 LSBGE Gain Error -0.1 0 0.1 %DNL Differential Non Linearity -0.93 0.4 +0.93 LSBINL Integral Non Linearity -1.8 0.8 +1.8 LSB
Mono tonicity and no missing codes Guaranteed
Symbol Parameter Min Typ Max Unit
GM Gain match 0.033 0.1 %OM Offset match 0.4 2.5 LSB
PHM Phase match 1 dgXTLK Crosstalk rejection 87 dB
TSA1204
7/20
DEFINITIONS OF SPECIFIED PARAMETERS
STATIC PARAMETERSStatic measurements are performed throughmethod of histograms on a 2MHz input signal,sampled at 20Msps, which is high enough to fullycharacterize the test frequency response. Theinput level is +1dBFS to saturate the signal.
Differential Non Linearity (DNL)The average deviation of any output code widthfrom the ideal code width of 1 LSB.
Integral Non linearity (INL)An ideal converter presents a transfer function asbeing the straight line from the starting code to theending code. The INL is the deviation for eachtransition from this ideal curve.
DYNAMIC PARAMETERSDynamic measurements are performed byspectral analysis, applied to an input sine wave ofvarious frequencies and sampled at 20Msps.The input level is -1dBFS to measure the linearbehavior of the converter. All the parameters aregiven without correction for the full scale ampli-tude performance except the calculated ENOBparameter.
Spurious Free Dynamic Range (SFDR)The ratio between the power of the worst spurioussignal (not always an harmonic) and the amplitudeof fundamental tone (signal power) over the fullNyquist band. It is expressed in dBc.
Total Harmonic Distortion (THD)The ratio of the rms sum of the first five harmonicdistortion components to the rms value of thefundamental line. It is expressed in dB.
Signal to Noise Ratio (SNR)The ratio of the rms value of the fundamentalcomponent to the rms sum of all other spectralcomponents in the Nyquist band (fs/2) excludingDC, fundamental and the first five harmonics.SNR is reported in dB.
Signal to Noise and Distortion Ratio (SINAD)Similar ratio as for SNR but including the harmonicdistortion components in the noise figure (not DCsignal). It is expressed in dB.From the SINAD, the Effective Number of Bits(ENOB) can easily be deduced using the formula:SINAD= 6.02 ENOB + 1.76 dB.When the applied signal is not Full Scale (FS), buthas an A0 amplitude, the SINAD expressionbecomes:SINAD2Ao=SINADFull Scale+ 20 log (2A0/FS)SINAD2Ao=6.02 ENOB + 1.76 dB + 20 log (2A0/FS)The ENOB is expressed in bits.
Analog Input BandwidthThe maximum analog input frequency at which thespectral response of a full power signal is reducedby 3dB. Higher values can be achieved withsmaller input levels.
Effective Resolution Bandwidth (ERB)The band of input signal frequencies that the ADCis intended to convert without loosing linearity i.e.the maximum analog input frequency at which theSINAD is decreased by 3dB or the ENOB by 1/2bit.
Pipeline delayDelay between the initial sample of the analoginput and the availability of the correspondingdigital data output, on the output bus. Also calleddata latency. It is expressed as a number of clockcycles.
TSA1204
8/20
Static parameter: Integral Non LinearityFs=20MSPS; Icca=40mA; Fin=2MHz
Static parameter: Differential Non LinearityFs=20MSPS; Icca=40mA; Fin=2MHz
Linearity vs. FsFin=5MHz; Rpol adjustment
Distortion vs. FsFin=5MHz; Rpol adjustment
-0.8
-0.6
-0.4
-0.2
0
0.2
0.4
0.6
0.8
0 500 1000 1500 2000 2500 3000 3500 4000
Output Code
INL
(LSB
s)
-0.4
-0.3
-0.2
-0.1
0
0.1
0.2
0.3
0.4
0 500 1000 1500 2000 2500 3000 3500 4000
Output Code
DN
L (L
SBs)
40
50
60
70
80
90
100
10 15 20 25
Fs (MHz)
Dyna
mic
par
amet
ers
(dB)
5
6
7
8
9
10
11
12
ENO
B (b
its)
ENOB I
SINAD_I
ENOB Q
SINAD_Q
SNR_I
SNR_Q
-120-110-100-90-80-70-60-50-40-30-20
10 15 20 25
Fs (MHz)
Dyna
mic
par
amet
ers
(dBc
)
THD_ISFDR_I
THD_QSFDR_Q
TSA1204
9/20
Linearity vs. FinFs=20MSPS; Icca=40mA
Linearity vs. TemperatureFs=20MSPS; Icca=40mA; Fin=2MHz
Linearity vs. AVCCFs=20MSPS; Icca=40mA; Fin=5MHz
Distortion vs. FinFs=20MSPS; Icca=40mA
Distortion vs. TemperatureFs=20MSPS; Icca=40mA; Fin=2MHz
Distortion vs. AVCCFs=20MSPS; Icca=40mA; Fin=5MHz
30
40
50
60
70
80
90
100
0 10 20 30 40 50
Fin (MHz)
Dyna
mic
par
amet
ers
(dB)
5
6
7
8
9
10
11
12
ENO
B (b
its)
ENOB_I
SNR_ISINAD_I
SNR_Q SINAD_Q
ENOB_Q
40
50
60
70
80
90
100
-40 10 60
Temperature (C)
Dyna
mic
par
amet
ers
(dB)
7
7.5
88.599.51010.511
11.512
ENO
B (b
its)
SINAD_QSNR_Q
ENOB_Q
ENOB_I
SNR_I SINAD_I
50556065707580859095
100
2.25 2.35 2.45 2.55 2.65
AVCC (V)
Dyna
mic
par
amet
ers
(dB)
6
7
8
9
10
11
12
ENO
B (b
its)
SINAD_I
ENOB_I
SNR_I
SNR_Q
ENOB_Q
SINAD_Q
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
0 10 20 30 40 50
Fin (MHz)
Dyn
amic
pa
ram
eter
s (d
Bc)
SFDR_I
SFDR_QTHD_I
THD_Q
40
50
60
70
80
90
100
110
120
-40 10 60
Temperature (C)
Dyna
mic
par
amet
ers
(dBc
)
THD_QSFDR_Q
THD_ISFDR_I
-120
-110
-100
-90
-80
-70
-60
-50
-40
-30
2.25 2.35 2.45 2.55 2.65
AVCC (V)
Dyn
amic
Pa
ram
eter
s (d
Bc)
SFDR_Q
SFDR_I
THD_Q
THD_I
TSA1204
10/20
Linearity vs. DVCCFs=20MSPS; Icca=40mA; Fin=5MHz
Linearity vs. VCCBIFs=20MSPS; Icca=40mA; Fin=5MHz
Linearity vs. VCCBEFs=20MSPS; Icca=40mA; Fin=5MHz
Distortion vs. DVCCFs=20MSPS; Icca=40mA; Fin=5MHz
Distortion vs. VCCBIFs=20MSPS; Icca=40mA; Fin=5MHz
Distortion vs. VCCBEFs=20MSPS; Icca=40mA; Fin=5MHz
40
50
60
70
80
90
100
2.25 2.35 2.45 2.55 2.65
DVCC (V)
Dyna
mic
par
amet
ers
(dB)
6
7
8
9
10
11
12
ENO
B (b
its)
SINAD_I
ENOB_I
SNR_ISNR_Q
ENOB_Q
SINAD_Q
50
55
60
65
70
75
80
85
90
2.25 2.35 2.45 2.55 2.65
VCCBI (V)
Dyna
mic
par
amet
ers
(dB)
8
8.5
9
9.5
10
10.5
11
11.5
12
ENO
B (b
its)
SINAD_I
ENOB_I
SNR_ISNR_Q
ENOB_Q
SINAD_Q
50
55
60
65
70
75
80
85
90
2.25 2.75 3.25
VCCBE (V)
Dyna
mic
par
amet
ers
(dB)
77.588.599.51010.51111.512
ENO
B (b
its)
SINAD_I
ENOB_I
SNR_Q
SNR_I
ENOB_Q
SINAD_Q
-120
-110
-100
-90
-80
-70
-60
-50
-40
2.25 2.35 2.45 2.55 2.65
DVCC (V)
Dyn
amic
Pa
ram
eter
s (d
Bc)
SFDR_Q
SFDR_I
THD_Q
THD_I
-120
-110
-100
-90
-80
-70
-60
-50
-40
2.25 2.35 2.45 2.55 2.65
VCCBI (V)
Dyn
amic
Pa
ram
eter
s (d
Bc)
SFDR_Q
SFDR_I
THD_Q
THD_I
-120
-110
-100
-90
-80
-70
-60
-50
-40
2.25 2.75 3.25
VCCBE (V)
Dyn
amic
Pa
ram
eter
s (d
Bc)
SFDR_Q
SFDR_I
THD_Q
THD_I
TSA1204
11/20
Linearity vs. Duty CycleFs=20MSPS; Icca=40mA; Fin=5MHz
Distortion vs. Duty CycleFs=20MSPS; Icca=40mA; Fin=5MHz
Single-tone 8K FFT at 20Msps - I ChannelFin=5MHz; Icca=40mA, Vin@-1dBFS
Dual-tone 8K FFT at 20Msps - I ChannelFin1=9.7MHz; Fin2=10.7MHz; Icca=40mA, Vin1@-7dBFS; Vin2@-7dBFS; IMD=-76dBc
40
50
60
70
80
90
100
45 47 49 51 53 55
Positive Duty Cycle (%)
Dyna
mic
par
amet
ers
(dB)
7
7.588.599.51010.51111.512
ENO
B (b
its)
SINAD_QSNR_Q
ENOB_Q
ENOB_I
SNR_I SINAD_I
-120
-110
-100
-90
-80
-70
-60
-50
-40
45 47 49 51 53 55
Positive Duty Cycle (%)
Dyna
mic
par
amet
ers
(dBc
)
THD_QSFDR_Q
THD_ISFDR_I
Frequency (MHz)1 2 3 4 6 7 8 9 105
-20
-40
-60
-100
-80
-140
0
-120Pow
er
spec
trum
(dB
)
-20
-40
-60
-100
-80
-140
0
-120
1 2 3 4 6 7 8 9 105Frequency (MHz)
Pow
er
spe
ctru
m (dB
)
12/20
TSA1204 APPLICATION NOTE
DETAILED INFORMATION
The TSA1204 is a dual-channel, 12-bit resolutionanalog to digital converter based on a pipelinestructure and the latest deep submicron CMOSprocess to achieve the best performances interms of linearity and power consumption.Each channel achieves 12-bit resolution throughthe pipeline structure which consists of 12 internalconversion stages in which the analog signal isfed and sequentially converted into digital data. Alatency time of 7 clock periods is necessary to ob-tain the digitized data on the output bus.The input signals are simultaneously sampled onboth channels on the rising edge of the clock. Theoutput data is valid on the rising edge of the clockfor I channel and on the falling edge of the clockfor Q channel. The digital data out from the differ-ent stages must be time delayed depending ontheir order of conversion. Then a digital data cor-rection completes the processing and ensures thevalidity of the ending codes on the output bus.The structure has been specifically designed toaccept differential signals only.
COMPLEMENTARY FUNCTIONS
Some functionalities have been added in order tosimplify as much as possible the applicationboard. These operational modes are described asfollowed.
Output Enable (OEB)When set to low level (VIL), all digital outputsremain active and are in low impedance state.When set to high level (VIH), all digital outputsbuffers are in high impedance state while theconverter goes on sampling. When OEB is set to alow level again, the data are then present on theoutput with a very short Ton delay.Therefore, this allows the chip select of the device.The timing diagram summarizes this functionality.In order to remain in the normal operating mode,this pin should be grounded through a low value ofresistor.
SELECTThe digital data out from each ADC cores are mul-tiplexed together to share the same output bus.This prevents from increasing the number of pinsand enables to keep the same package as singlechannel ADC like TSA1201.The selection of the channel information is donethrough the "SELECT" pin. When set to high level(VIH), the I channel data are present on the busD0-D11. When set to low level (VIL), the Q chan-nel data are on the output bus D0-D11.Connecting SELECT to CLK allows I and Q chan-nels to be simultaneously present on D0-D11; Ichannel on the rising edge of the clock and Qchannel on the falling edge of the clock. (see tim-ing diagram page 2).REFERENCES AND COMMON MODE CONNECTION
VREFM must be always connected externally.
Internal reference and common modeIn the default configuration, the ADC operates withits own reference and common mode voltagesgenerated by its internal bandgap. VREFM pinsare connected externally to the Analog Groundwhile VREFP (respectively INCM) are set to theirinternal voltage of 0.89V (respectively 0.46V). It isrecommended to decouple the VREFP and INCMpins in order to minimize low and high frequencynoise (refer to Figure 1)Figure 1 : Internal reference and common mode setting
TSA1204VIN
VINBVREFM
1.03V
VREFP330pF 4.7uF10nF
INCM330pF 4.7uF10nF0.57V
TSA1204
13/20
External reference and common modeEach of the voltages VREFM, VREFP and INCMcan be fixed externally to better fit to theapplication needs (Refer to table OPERATINGCONDITIONS page 4 for min/max values).The VREFP, VREFM voltages set the analogdynamic at the input of the converter that has a fullscale amplitude of 2*(VREFP-VREFM). Usinginternal VREFP, the dynamic range is 1.8V.The best linearity and distortion performances areachieved with a dynamic range above 2Vpp andby increasing the VREFM voltage instead oflowering the VREFP one.The INCM is the mid voltage of the analog inputsignal.It is possible to use an external reference voltagedevice for specific applications requiring evenbetter linearity, accuracy or enhancedtemperature behavior.Using the STMicroelectronics TS821orTS4041-1.2 Vref leads to optimum performanceswhen configured as shown on Figure 2.
Figure 2 : External reference setting
DRIVING THE DIFFERENTIAL ANALOG INPUTSThe TSA1204 has been designed to obtainoptimum performances when being differentiallydriven. An RF transformer is a good way toachieve such performances.Figure 3 describes the schematics. The inputsignal is fed to the primary of the transformer,while the secondary drives both ADC inputs. Thecommon mode voltage of the ADC (INCM) isconnected to the center-tap of the secondary ofthe transformer in order to bias the input signalaround this common voltage, internally set to0.46V. It determines the DC component of theanalog signal. As being an high impedance input,it acts as an I/O and can be externally driven toadjust this DC component. The INCM isdecoupled to maintain a low noise level on this
node. Our evaluation board is mounted with a 1:1ADT1-1WT transformer from Minicircuits. Youmight also use a higher impedance ratio (1:2 or1:4) to reduce the driving requirement on theanalog signal source.Each analog input can drive a 1.4Vpp amplitudeinput signal, so the resultant differential amplitudeis 2.8Vpp.Figure 3 : Differential input configuration with transformer
Figure 4 represents the biasing of a differentialinput signal in AC-coupled differential inputconfiguration. Both inputs VIN and VINB arecentered around the common mode voltage, thatcan be let internal or fixed externally.
Figure 4 : AC-coupled differential input
Figure 5 shows a DC-coupled configuration withforced VREFP and INCM to the 1V DC analoginput while VREFM is connected to ground; weachieve a 2Vpp differential amplitude.
1k
TSA1204VIN
VINBVREFM
VREFP
externalreference
VCCA330pF 4.7uF10nF
TS821TS4041
TSA1204VIN
VINB
INCM
50 33pF
330pF 470nF10nF
Analog source 1:1ADT1-1
I or Q ch.
50 10nF
TSA1204
VIN
VINB
INCM33pF100k
100k
50 10nF
commonmode
TSA1204
14/20
Figure 5 : DC-coupled 2Vpp differential analog input
Clock input
The TSA1204 performance is very dependant onyour clock input accuracy, in terms of aperturejitter; the use of low jitter crystal controlledoscillator is recommended.The duty cycle must be between 45% and 55%.The clock power supplies must be separated fromthe ADC output ones to avoid digital noisemodulation at the output.It is recommended to always keep the circuitclocked, even at the lowest specified samplingfrequency of 0.5Msps, before applying the supplyvoltages.
Power consumption
So as to optimize both performance and powerconsumption of the TSA1204 according thesampling frequency, a resistor is placed betweenIPOL and the analog Ground pins. Therefore, thetotal dissipation is adjustable from 10Msps up to20Msps. The TSA1204 will combine highest performancesand lowest consumption at 20Msps when Rpol isequal to 54k.At lower sampling frequency range, this value ofresistor may be adjusted in order to decrease theanalog current without any degradation ofdynamic performances.The table below sums up the relevant data.
Figure 6 : Total power consumption optimizationdepending on Rpol value
Layout precautions
To use the ADC circuits in the best manner at highfrequencies, some precautions have to be takenfor power supplies:- First of all, the implementation of 4 separateproper supplies and ground planes (analog,digital, internal and external buffer ones) on thePCB is recommended for high speed circuitapplications to provide low inductance and lowresistance common return. The separation of the analog signal from thedigital part is mandatory to prevent noise fromcoupling onto the input signal. The bestcompromise is to connect from one part AGND,DGND, GNDBI in a common point whereasGNDBE must be isolated. Similarly, the powersupplies AVCC, DVCC and VCCBI must beseparated from the VCCBE one. - Power supply bypass capacitors must be placedas close as possible to the IC pins in order toimprove high frequency bypassing and reduceharmonic distortion. - Proper termination of all inputs and outputs mustbe incorporated with output termination resistors;then the amplifier load will be only resistive andthe stability of the amplifier will be improved. Allleads must be wide and as short as possibleespecially for the analog input in order to decreaseparasitic capacitance and inductance.- To keep the capacitive loading as low aspossible at digital outputs, short lead lengths ofrouting are essential to minimize currents whenthe output changes. To minimize this outputcapacitance, buffers or latches close to the outputpins will relax this constraint. - Choose component sizes as small as possible(SMD).APPLICATIONDigital Interface applicationThanks to its wide external buffer power supplyrange, the TSA1204 is perfectly suitable to plug into 2.5V low voltage DSPs or digital interfaces aswell as to 3.3V ones.Medical Imaging applicationDriven by the demand of the applications requiringnowadays either portability or high degree of par-allelism (or both), this product has been devel-oped to satisfy medical imaging, and telecom in-frastructures needs.As a typical system diagram shows figure 7, a nar-row input beam of acoustic energy is sent into aliving body via the transducer and the energy re-flected back is analyzed.
Fs (Msps) 10 20Rpol (k) 120 54Optimized power (mW)
95 120
TSA1204VIN
VINB
INCM
330pF 4.7uF10nF
analog
DC
AC+DC VREFP
VREFM
DCanalog
VREFP-VREFM = 1 V
TSA1204
15/20
Figure 7 : Medical imaging application
The transducer is a piezoelectric ceramic such aszirconium titanate. The whole array can reach upto 512 channels.
The TX beam former, amplified by the HV TXamps, delivers up to 100V amplitude excitationpulses with phase and amplitude shifts.The mux and T/R switch is a two way input signaltransmitter/ output receiver.To compensate for skin and tissues attenuationeffects, The Time Gain Compensation (TGC) am-plifier is an exponential amplifier that enables theamplification of low voltage signals to the ADC in-put range. Differential output structure with low
noise and very high linearity are mandatory fac-tors. These applications need high speed, low powerand high performance ADCs. 10-12 bit resolution is necessary to lower the quantificationnoise. As multiple channels are used, a dual con-verter is a must for room saving issues. The input signal is in the range of 2 to 20MHz(mainly 2 to 7MHz) and the application uses most-ly a 4 over-sampling ratio for Spurious Free Dy-namic Range (SFDR) optimization. The next RX beam former and processing blocksenable the analysis of the outputs channels ver-sus the input beam.
EVAL1204/BA evaluation board
The EVAL1204/BA is a 4 layer board with highdecoupling and grounding level. The schematic ofthe evaluation board is reported figure 11 and itstop overlay view figure 10. The characterization ofthe board has been made with a fully ADCdevoted test bench as shown on Figure 8. Theanalog signal must be filtered to be very pure.The dataready signal is the acquisition clock of thelogic analyzer.The ADC digital outputs are latched by the octalbuffers 74LCX573.All characterization measurements have beenmade with:- SFSR=1dB for static parameters.
Figure 8 : Analog to Digital Converter characterization bench
Mux andT/Rswitches
TX beamformer
Processingand display
RX beamformerADC
TGC amplifier
HV TX amps
Sine Wave Generator
HP8644
ADC evaluation
board
Pulse Generator
Logic Analyzer
Sine Wave GeneratorHP8644
HP8133
Vin
Clk
Data
ClkPC
TSA1204
16/20
Operating conditions of the evaluation board:Find below the connections to the board for thepower supplies and other pins:
Care should be taken for the evaluation board asthe outputs of the converter are 2.5V/3.3V(VCCB2) tolerant whereas the 74LCX573 externalbuffers are operating up to 2.5V.
Single and Differential Inputs:The ADC board components are mounted to testthe TSA1204 with single analog input; theADT1-1WT transformer enables the differentialdrive into the converter; in this configuration, theresistors RSI6, RSI7, RSI8 for I channel (respec-tively RSQ6, RSQ7, RSQ8 for Q one) are con-nected as short circuits whereas RSI5, RSI9 (re-spectively RSQ5, RSQ9) are open circuits.The other way is to test it via JI1 and JI1B differential inputs. So, the resistances RSI5, RSI9 for I channel (respectively RSQ5, RSQ9 for Q one) are connected as short circuits whereas RSI6, RSI7, RSI8 (respectively RSQ6, RSQ7, RSQ8 for Q one) are open circuits.
Grounding consideration
So as to better reject noise on the board, connect on the bottom overlay AG (AGND), DG(DGND), GB1(GNDBI) together from one part, and GB2(GNDBE) with GB3(GNDB3) from the other part.
Mode selectSo as to evaluate a single channel or the dualones, you have to connect on the board therelevant position for the SELECT pin.With the strap connected - to the upper connectors, the I channel at the out-put is selected.- horizontally, the Q channel at the output is se-lected- to the lower connectors, both channels are se-lected, relative to the clock edge.
Figure 9 : mode select
Consumption adjustmentBefore any characterization, care should be takento adjust the Rpol (Raj1) and therefore Ipol valuein function of your sampling frequency.
board notation
connection internal voltage (V)
external voltage (V)
AV AVCC 2.5
AG AGND 0
RPI REFPI 0.89
TSA1204
17/20
Figure 10 : Printed circuit of evaluation board.
TSA1204
18/20
Figure 11 : TSA1204 Evaluation board schematic
RI1
50
R2 1K
R3
50
CI1
33pF
C2 330p
F
C3 470n
F
C4 10nF
CI8
330p
F
CI9
10nF
CI10
470n
FCI
11
330p
F
CI12
10nF
CI13
470n
F
C14
330p
F
C15
10nF
C16
470n
F
Raj1
47K
C17
330p
F
C18
10nF
C19
470n
F
J4 CLK
OEB
1
D0
2D
13
D2
4
D3
5D
46
D5
7
D6
8D
79
GND
10LE
11
Q019
Q118
Q217
Q316
Q415
Q514
Q613
Q712
VCC
20
U2
74LC
X57
3
OEB
1D
02
D1
3D
24
D3
5D
46
D5
7D
68
D7
9GN
D10
LE11
Q019
Q118
Q217
Q316
Q415
Q514
Q613
Q712
VCC
20
U3
74LC
X57
3
R11
47K
C25
330p
F
C27
10nF
C28
470n
F
+
C29
10F
DO D7 D8 D9 D10
D11
CI30
330p
F
CI31
10nF
CI32
470n
F
+
C34
47F
+
C35
47F
AVCC
VCCB
2
VCCB
1
C26
330p
F
C39
10nF
C37
470n
F
VCCB
3
C33
330p
F
C40
10nF
C38
470n
F
C41
10F
+C4
247
F
CLK
D1
D2
D3
D4
D5
D6
C20
330p
F
C21
10nF
C22
470n
F
C23
10F
+
C36
47F
1
43
26TI
2
T2-AT
1-1W
T
JI1B
InIB
R5 50
J25
CKD
ATA
12J2
7
CON2
RI19
50
S4SW
-SP
STVCC
B1
GndB1
VccB1
GndB2
VccB2
GndB3
VccB3
J17
BUFP
OW
D0
GND
D1
GND
D2
GND
D3
GND
D4
GND
D5
GND
D6
GND
D7
GND
D8
GND
D9
GND
D10
GN
D
D11
GN
D
CLK
GN
D
AVCC
C5
100n
F
CI6
NM
VCCB
2
C51
330p
F
C52
10nF
C53
470n
FRS
I5 0 NC
RSI6 0
RSI7
0
RSI8
0 RSI9
0 NC
NM
: non s
oud
analo
g inp
utw
ith tr
ansf
orm
er (de
fault)
RS5
RS
6 RS
7 RS
8 RS
9 C
C
C
C C
C C
single
inp
utdif
fere
ntia
l inpu
t
12
J26
CON2
AGND
1
INI
2AG
ND3
INBI
4AG
ND5
IPOL
6AV
CC7
AGND
8IN
Q9
AGND
10IN
BQ11
AGND
12
REFPQ
13
REFMQ
14
INCMQ
15
AGND
16
AVCC
17
DVCC
18
DGND
19
CLK
20
SELECT
21
DGND
22
DVCC
23
GNDBI
24
GNDB
E25
VCCB
E26
D11
(MSB
)27
D10
28D
929
D8
30D
731
D6
32D
533
D4
34D
335
D2
36
D1
37
D0(LSB)
38
VCCBE
39
GNDBE
40
VCCBI
41
VCCBI
42
OEB
43
AVCC
44
AVCC
45
INCMI
46
REFMI
47
REFPI
48
8-14
bits
ADC
J9
ADC
DUA
L12B C
D3
330p
F
CD2
10nF
CD1
470n
F
1 Q
RQ1
50
CQ1
33pF
CQ8
330p
F
CQ9
10nF
CQ10
470n
F
CQ11
330p
F
CQ12
10nF
CQ13
470n
FCQ
30
330p
F
CQ31
10nF
CQ32
470n
F
1
43
26TQ
2
T2-AT
1-1W
T
JQ1B
InQB
RQ19
50
CQ6
NM
RSQ5 0 N
CRS
Q6 0RS
Q70 RS
Q80
RSQ9
0 NC
AVCC
C10
330p
F
C11
10nF
C13
470n
F
C31
10F
+
C32
47F
DVC
C
DVC
CDVc
c
R21
0NM
R22
0NM
R23
0NM
R24
0NM
REFP
REFM
INCM
JI2
VREF
I
REFP
REFM
INCM
JQ2
VREF
Q
GND
VCC
JA ANAL
OGIC
GND
VCC
JDDIG
ITAL
VCCB
1
SW1
S5 SW-SP
ST
IN Vcc
GND
S1S2 D
U1 STG7
19
VCCB
2
VCCB
2
R12
47K
C43
10F
+
C44
47F
VCCB
3
VCCB
2Sw
itch
S4 OE
B M
ode
Open
N
orm
al m
ode
Shor
t Hi
gh Im
peda
nce
outp
ut m
ode
1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 29 30 31 32
J6
Switc
h S5
Open
N
orm
al m
ode
Short
Te
st m
ode
TSA1204
19/20
Figure 12 : Printed circuit board - List of components Name Footprint Name Footprint Name Footprint Name Part Footprint
TypeRSQ6 0 805 CD2 10nF 603 C26 330pF 603 CQ6 NC 805RSQ7 0 805 C40 10nF 603 C20 330pF 603 CI6 NC 805RSQ8 0 805 C39 10nF 603 C33 330pF 603 U2 74LCX573 TSSOP20RSI6 0 805 CQ12 10nF 603 C25 330pF 603 U3 74LCX573 TSSOP20RSI7 0 805 CQ9 10nF 603 CI1 33pF 603 U1 STG719 SOT23-6RSI8 0 805 C52 10nF 603 CQ1 33pF 603 JA ANALOGIC connectorR3 47 603 C18 10nF 603 C34 47F RB.1 J17 BUFPOW connectorR5 47 603 C21 10nF 603 C42 47F RB.1 J25 CKDATA SMARQ19 47 603 C4 10nF 603 C35 47F RB.1 J4 CLK SMARI1 47 603 C15 10nF 603 C44 47F RB.1 J27 CON2 SIP2RQ1 47 603 C27 10nF 603 C36 47F RB.1 J26 CON2 SIP2 RI19 47 603 C11 10nF 603 C32 47F RB.1 JD DIGITAL connectorRSI9 0NC 805 CI9 10nF 603 C37 470nF 805 JI1 InI SMARSQ5 0NC 805 CI12 10nF 603 CQ10 470nF 805 JI1B InIB SMARSQ9 0NC 805 CI31 10nF 603 C28 470nF 805 JQ1 InQ SMARSI5 0NC 805 CQ31 10nF 603 CI10 470nF 805 JQ1B InQB SMAR24 0NC 805 CQ30 330pF 603 CQ32 470nF 805 SW1 SWITCH connectorR23 0NC 805 CI11 330pF 603 CQ13 470nF 805 S5 SW-SPST connectorR21 0NC 805 C51 330pF 603 CI32 470nF 805 S4 SW-SPST connectorR22 0NC 805 C2 330pF 603 C13 470nF 805 TI2 T2-AT1-1WT ADTR2 1K 603 C17 330pF 603 C53 470nF 805 TQ2 T2-AT1-1WT ADTR12 47K 603 CD3 330pF 603 C16 470nF 805 JI2 VREFI connectorR11 47K 603 C10 330pF 603 C3 470nF 805 JQ2 VREFQ connectorRaj1 200K CQ8 330pF 603 C22 470nF 805 J6 32Pin
CQ11 330pF 603 CI13 470nF 805C23 10F 1210 CI8 330pF 603 C38 470nF 805C41 10F 1210 C14 330pF 603 CD1 470nF 805 NC: non solderedC29 10F 1210 CI30 330pF 603 C19 470nF 805
VR5 trimmer
IDC-32 connector
Part Type
Part Type
Part Type
TSA1204
20/20
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for theconsequences of use of such information nor for any infringement of patents or other rights of third parties which may result fromits use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specificationsmentioned in this publication are subject to change without notice. This publication supersedes and replaces all informationpreviously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices orsystems without express written approval of STMicroelectronics.
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PACKAGE MECHANICAL DATA48 PINS - PLASTIC PACKAGE
Dim.Millimeters Inches
Min. Typ. Max. Min. Typ. Max.A 1.60 0.063A1 0.05 0.15 0.002 0.006A2 1.35 1.40 1.45 0.053 0.055 0.057B 0.17 0.22 0.27 0.007 0.009 0.011C 0.09 0.20 0.004 0.008D 9.00 0.354D1 7.00 0.276D3 5.50 0.216e 0.50 0.0197E 9.00 0.354E1 7.00 0.276E3 5.50 0.216L 0.45 0.60 0.75 0.018 0.024 0.030
L1 1.00 0.039K 0 (min.), 7 (max.)
48 37
D3
e
13 24
1
12 25
36
c
A1A2A
D1D
E3 E1 EL
K
L1
0,25 mm.010 inchGAGE PLANE
0,10 mm.004 inch
SEATING PLANE
B