CHEE 434/821 Process Control II Some Review Material Winter 2006 Instructor:M.GuayTA: V. Adetola
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CHEE 434/821 CHEE 434/821 Process Control II Process Control II Some Review Material Some Review Material Winter 2006 Winter 2006 Instructor: Instructor: M.Guay M.Guay TA: TA: V. Adetola V. Adetola
CHEE 434/821 Process Control II Some Review Material Winter 2006 Instructor:M.GuayTA: V. Adetola
CHEE 434/821 Process Control II Some Review Material Winter
2006 Instructor:M.GuayTA: V. Adetola
Slide 2
Introduction In the chemical industry, the design of a control
system is essential to ensure: Good Process Operation Process
Safety Product Quality Minimization of Environmental Impact
Slide 3
Introduction n What is the purpose of a control system? To
maintain important process characteristics at desired targets
despite the effects of external perturbations. Control Plant
Processingobjectives Safety Make $$$ Environment... Perturbations
Market Economy Climate Upsets...
Slide 4
Introduction Plant Control What constitutes a control system?
Combination of process sensors, actuators and computer systems
designed and tuned to orchestrate safe and profitable
operation.
Slide 5
Introduction n n Process Dynamics: Study of the transient
behavior of processes n n Process Control the use of process
dynamics for the improvement of process operation and performance
or the use of process dynamics to alleviate the effect of
undesirable (unstable) process behaviors
Slide 6
Introduction What do we mean by process? A process, P, is an
operation that takes an INPUT or a DISTURBANCE and gives an OUTPUT
INPUT: (u) Something that you can manipulate DISTURBANCE: (d)
Something that comes as a result of some outside phenomenon OUTPUT:
(y) An observable quantity that we want to regulate u d y P
Information Flow
Slide 7
Examples n n Stirred tank heater M T in, w Q T, w T in w Q
TProcess Inputs Output
Slide 8
Examples n n The speed of an automobile Force of Engine
Friction Inputs Output Friction Engine SpeedProcess
Slide 9
Examples e.g. Landing on Mars
Slide 10
Examples e.g. Millirobotics Laparoscopic Manipulators
Slide 11
Introduction n n Process A process, P, is an operation that
takes an INPUT or a DISTURBANCE and gives an OUTPUT INPUT: (u)
Something that you can manipulate DISTURBANCE: (d) Something that
comes as a result of some outside phenomenon OUTPUT: (y) An
observable quantity that we want to regulate u d y P Information
Flow
Slide 12
Control What is control? n n To regulate of a process output
despite the effect of disturbances e.g. Driving a car Controlling
the temperature of a chemical reactor Reducing vibrations in a
flexible structure n n To stabilize unstable processes e.g. Riding
a bike Flight of an airplane Operation of a nuclear plant
Slide 13
Benefits of Control n n Economic Benefits Quality (waste
reduction) Variance reduction (consistency) Savings in energy,
materials, manpower n n Operability, safety (stability) Performance
Efficiency Accuracy l l robotics Reliability Stabilizability l l
bicycle l l aircraft l l nuclear reactor
Slide 14
Control n A controller is a system designed to regulate a given
process Process typically obeys physical and chemical conservation
laws Controller obeys laws of mathematics and logic (sometimes
intelligent) e.g. - Riding a bike (human controller) - Driving a
car - Automatic control (computer programmed to control) Process
Controller What is a controller?
Slide 15
Block representations n n Block diagrams are models of the
physical systems Process System Physical Boundary Transfer of
fundamental quantities Mass, Energy and Momentum Input variables
Output variables Physical Operation Abstract
Slide 16
Control n n A controlled process is a system which is comprised
of two interacting systems: e.g. Most controlled systems are
feedback controlled systems The controller is designed to provide
regulation of process outputs in the presence of disturbances
Process Controller OutputsDisturbances ActionObservation
monitorintervene
Slide 17
Introduction What is required for the development of a control
system? 1. The Plant (e.g. SPP of Nylon) Water Steam Gas Make-up
Vent Nylon Blower Dehumidifier Reheater Relief Pot Heater
Slide 18
Introduction What is required? 1. Process Understanding
Required measurements Required actuators Understand design
limitations 2. Process Instrumentation Appropriate sensor and
actuator selection Integration in control system Communication and
computer architecture 3. Process Control Appropriate control
strategy
Slide 19
Example n n Cruise Control Controller Friction Process Speed
Engine Human or Computer
Slide 20
Classical Control n n Control is meant to provide regulation of
process outputs about a reference, r, despite inherent disturbances
n n The deviation of the plant output, e=(r-y), from its intended
reference is used to make appropriate adjustments in the plant
input, u ProcessController Classical Feedback Control System d yure
+ -
Slide 21
Control n n Process is a combination of sensors and actuators n
n Controller is a computer (or operator) that performs the required
manipulations e.g. Classical feedback control loop yre ACP M d
ComputerActuator Process Sensor - +
Slide 22
Examples n n Driving an automobile ye ACP M Driver Automobile -
+ Steering r Visual and tactile measurement Desired trajectory r
Actual trajectory y
Slide 23
Examples n n Stirred-Tank Heater T in, w QT, w Heater TC
Thermocouple ye ACP M Controller Tank - + Heater Thermocouple T in,
w TRTR
Slide 24
Examples n n Measure T, adjust Q Controller:Q=K(T R -T)+Q
nominal whereQ nominal =wC(T-T in ) Q: Is this positive or negative
feedback? T in, w Te ACP M Controller Tank - + Heater Thermocouple
Feedback control TRTR
Slide 25
Examples n n Measure T i, adjust Q APC M TiTi QiQi QQ Q + +
Feedforward Control
Slide 26
Control Nomenclature n n Identification of all process
variables Inputs(affect process) Outputs(result of process) n n
Inputs Disturbance variables Variables affecting process that are
due to external forces Manipulated variables Things that we can
directly affect
Slide 27
Control Nomenclature n n Outputs Measured speed of a car
Unmeasured acceleration of a car Control variables important
observable quantities that we want to regulate can be measured or
unmeasured Controller Manipulated Disturbances Process Control
Other
Slide 28
Example T L T w i, T i w c, T ci w c, T co w o, T o h Variables
w i, w o :Tank inlet and outlet mass flows T i, T o :Tank inlet and
outlet temperatures w c :Cooling jacket mass flow P c :Position of
cooling jacket inlet valve P o :Position of tank outlet valve T ci,
T co :Cooling jacket inlet and outlet temperatures h:Tank liquid
level PoPo PcPc
Slide 29
Example Variables InputsOutputs Disturbances Manipulated
Measured Unmeasured Control w i T i T ci w c h w o T o P c P o
Task: Classify the variables
Slide 30
Process Control and Modeling n n In designing a controller, we
must Define control objectives Develop a process model Design
controller based on model Test through simulation Implement to real
process Tune and monitor Model Controller yure d Process Design
Implementation
Slide 31
Control System Development Define Objectives Develop a process
model Design controller based on model Test by Simulation Implement
and Tune Monitor Performance Control development is usually carried
out following these important steps Often an iterative process,
based on performance we may decide to retune, redesign or remodel a
given control system
Slide 32
Control System Development n n Objectives What are we trying to
control? n n Process modeling What do we need? Mechanistic and/or
empirical n n Controller design How do we use the knowledge of
process behavior to reach our process control objectives? What
variables should we measure? What variables should we control? What
are the best manipulated variables? What is the best controller
structure?
Slide 33
Control System Development n n Implement and tune the
controlled process Test by simulation incorporate control strategy
to the process hardware theory rarely transcends to reality tune
and re-tune n n Monitor performance periodic retuning and redesign
is often necessary based on sensitivity of process or market
demands statistical methods can be used to monitor performance
Slide 34
Process Modeling n n Motivation: Develop understanding of
process a mathematical hypothesis of process mechanisms Match
observed process behavior useful in design, optimization and
control of process n n Control: Interested in description of
process dynamics Dynamic model is used to predict how process
responds to given input Tells us how to react
Slide 35
Process Modeling What kind of model do we need? n n Dynamic vs.
Steady-state Steady-state Variables not a function of time useful
for design calculation Dynamic Variables are a function of time
Control requires dynamic model
Slide 36
Process Modeling What kind of model do we need? n n
Experimental vs Theoretical Experimental Derived from tests
performed on actual process Simpler model forms Easier to
manipulate Theoretical Application of fundamental laws of physics
and chemistry more complex but provides understanding Required in
design stages
Slide 37
Process Modeling n Dynamic vs. Steady-state n Step change in
input to observe Starting at steady-state, we made a step change
The system oscillates and finds a new steady- state Dynamics
describe the transitory behavior 0 50100150200250300 40 45 50 55 60
65 Output Time Steady-State 1 Steady-State 2
Slide 38
Process Modeling n n Empirical vs. Mechanistic models Empirical
Models only local representation of the process (no extrapolation)
model only as good as the data Mechanistic Models Rely on our
understanding of a process Derived from first principles Observing
laws of conservation of l l Mass l l Energy l l Momentum Useful for
simulation and exploration of new operating conditions May contain
unknown constants that must be estimated
Slide 39
Process Modeling n n Empirical vs Mechanistic models Empirical
models do not rely on underlying mechanisms Fit specific function
to match process Mathematical French curve
Slide 40
Process Modeling n n Linear vs Nonlinear Linear basis for most
industrial control simpler model form, easy to identify easy to
design controller poor prediction, adequate control Nonlinear
reality more complex and difficult to identify need
state-of-the-art controller design techniques to do the job better
prediction and control n n In existing processes, we really on
Dynamic models obtained from experiments Usually of an empirical
nature Linear n n In new applications (or difficult problems) Focus
on mechanistic modeling Dynamic models derived from theory
Nonlinear
Slide 41
Process Modeling n n General modeling procedure Identify
modeling objectives end use of model (e.g. control) Identify
fundamental quantities of interest Mass, Energy and/or Momentum
Identify boundaries Apply fundamental physical and chemical laws
Mass, Energy and/or Momentum balances Make appropriate assumptions
(Simplify) ideality (e.g. isothermal, adiabatic, ideal gas, no
friction, incompressible flow, etc,) Write down energy, mass and
momentum balances (develop the model equations)
Slide 42
Process Modeling n n Modeling procedure Check model consistency
do we have more unknowns than equations Determine unknown constants
e.g. friction coefficients, fluid density and viscosity Solve model
equations typically nonlinear ordinary (or partial) differential
equations initial value problems Check the validity of the model
compare to process behavior
Slide 43
Process Modeling n n For control applications: Modeling
objectives is to describe process dynamics based on the laws of
conservation of mass, energy and momentum n n The balance equation
1. Mass Balance (Stirred tank) 2. Energy Balance (Stirred tank
heater) 3. Momentum Balance (Car speed) Rate of Accumulation of
fundamental quantity Flow In Flow Out Rate of Production = - +
Slide 44
Process Modeling n n Application of a mass balance Holding Tank
n n Modeling objective: Control of tank level n n Fundamental
quantity: Mass n n Assumptions: Incompressible flow h F F in
Slide 45
Process Modeling Total mass in system = Total mass in system =
V = Ah Flow in = Flow in = F in Flow out = Flow out = F Total mass
at time t = Ah(t) Total mass at time = Total mass at time t+ t =
Ah(t t Accumulation = Ah(t t Ah(t) = t( F in - F ),
Slide 46
Process Modeling Model consistency Can we solve this equation?
Variables: h, , F in, F, A5 Constants: , A2 Inputs: F in, F2
Unknowns:h1 Equations1 Degrees of freedom0 There exists a solution
for each value of the inputs F in, F
Slide 47
Process Modeling Solve equation Specify initial conditions
h(0)=h 0 and integrate
Slide 48
Process Modeling n n Energy balance Objective:Control tank
temperature Fundamental quantity: Energy Assumptions:Incompressible
flow Constant hold-up M T in, w Q T, w
Slide 49
Process Modeling n n Under constant hold-up and constant mean
pressure (small pressure changes) Balance equation can be written
in terms of the enthalpies of the various streams Typically work
done on system by external forces is negligible Assume that the
heat capacities are constant such that
Slide 50
Process Modeling After substitution, Since T ref is fixed and
we assume constant ,C p Divide by C p V
Slide 51
Process Modeling Resulting equation: Model Consistency
Variables: T, F, V, T in, Q, C p, 7 Constants: V, C p, 3 Inputs: F,
T in, Q3 Unknown: T1 Equations1 There exists a unique solution
Slide 52
Process Modeling Assume F is fixed where V/F is the tank
residence time (or time constant) If F changes with time then the
differential equation does not have a closed form solution. Product
F(t)T(t) makes this differential equation nonlinear. Solution will
need numerical integration.
Slide 53
Process Modeling A simple momentum balance Objective:
Objective:Control car speed Quantity Quantity:Momentum Assumption
Assumption:Friction proportional to speed MomentumOut = Sum of
forces acting on system MomentumIn Rate of Accumulation - + Force
of Engine (u) Friction Speed (v)
Slide 54
Process Modeling Forces are:Force of the engine = u Friction =
bv Balance: Total momentum = Mv Model consistency Variables:M, v,
b, u4 Constants:M, b2 Inputs:u1 Unknownsv1
Slide 55
Process Modeling n n Gravity tank Objectives: Objectives:
height of liquid in tank Fundamental quantity: Fundamental
quantity: Mass, momentumAssumptions: Outlet flow is driven by head
of liquid in the tank Incompressible flow Plug flow in outlet pipe
Turbulent flow h L F FoFo
Slide 56
Process Modeling From mass and momentum balances, A system of
simultaneous ordinary differential equations results Linear or
nonlinear?
Slide 57
Process Modeling Model consistency VariablesF o, A, A p, v, h,
g, L, K F, Constants A, A p, g, L, K F, Inputs F o 1 Unknownsh, v2
Equations2 Model is consistent
Slide 58
Solution of ODEs n n Mechanistic modeling results in nonlinear
sets of ordinary differential equations n n Solution requires
numerical integration n n To get solution, we must first: specify
all constants (densities, heat capacities, etc, ) specify all
initial conditions specify types of perturbations of the input
variables For the heated stirred tank, specify C P, and V specify
T(0) specify Q(t) and F(t)
Slide 59
Input Specifications n n Study of control system dynamics
Observe the time response of a process output in response to input
changes n n Focus on specific inputs 1. Step input signals 2. Ramp
input signals 3. Pulse and impulse signals 4. Sinusoidal signals 5.
Random (noisy) signals
Slide 60
Common Input Signals 1. Step Input Signal: a sustained
instantaneous change e.g. Unit step input introduced at time 1
Slide 61
Common Input Signals 2. Ramp Input: A sustained constant rate
of change e.g.
Slide 62
Common Input Signals 3. Pulse: An instantaneous temporary
change e.g. Fast pulse (unit impulse)
Slide 63
Common Input Signals 3. Pulses: e.g. Rectangular Pulse
Slide 64
Common Input Signals 4. Sinusoidal input
Slide 65
Common Input Signals 5. Random Input
Slide 66
Solution of ODEs using Laplace Transforms Process Dynamics and
Control
Slide 67
Linear ODEs n n For linear ODEs, we can solve without
integrating by using Laplace transforms n n Integrate out time and
transform to Laplace domain Multiplication Y(s) = G(s)U(s)
Integration
Slide 68
Common Transforms Useful Laplace Transforms 1. Exponential 2.
Cosine
Slide 69
Common Transforms Useful Laplace Transforms 3. Sine
Slide 70
Common Transforms Operators 1. Derivative of a function f(t) 2.
Integral of a function f(t)
Slide 71
Common Transforms Operators 3. Delayed function f(t- )
Slide 72
Common Transforms Input Signals 1. Constant 2. Step 3. Ramp
function
Slide 73
Common Transforms Input Signals 4. Rectangular Pulse 5. 5. Unit
impulse
Slide 74
Laplace Transforms Final Value TheoremLimitations: Initial
Value Theorem
Slide 75
Solution of ODEs We can continue taking Laplace transforms and
generate a catalogue of Laplace domain functions. See SEM Table 3.1
The final aim is the solution of ordinary differential
equations.Example Using Laplace Transform, solve Result
Slide 76
Solution of Linear ODEs Stirred-tank heater (with constant F)
taking Laplace To get back to time domain, we must Specify Laplace
domain functions Q(s), T in (s) Take Inverse Laplace
Slide 77
Linear ODEs Notes: The expression describes the dynamic
behavior of the process explicitly The Laplace domain functions
multiplying T(0), T in (s) and Q(s) are transfer functions + + + T
in (s) Q(s) T(0) T(s)
Slide 78
Laplace Transform Assume T in (t) = sin( t) then the transfer
function gives directly Cannot invert explicitly, but if we can
find A and B such that we can invert using tables. Need Partial
Fraction Expansion to deal with such functions
Slide 79
Linear ODEs We deal with rational functions of the form
r(s)=p(s)/q(s) where degree of q > degree of p q(s) is called
the characteristic polynomial of the function r(s) Theorem: Every
polynomial q(s) with real coefficients can be factored into the
product of only two types of factors powers of linear terms (x-a) n
and/or powers of irreducible quadratic terms, (x 2 +bx+c) m
Slide 80
Partial fraction Expansions 1. q(s) has real and distinct
factors expand as 2. q(s) has real but repeated factor
expanded
Slide 81
Partial Fraction Expansion Heaviside expansion For a rational
function of the form Constants are given by Note: Most applicable
to q(s) with real and distinct roots. It can be applied to more
specific cases.
Slide 82
Partial Fraction Expansions 3. Q(s) has irreducible quadratic
factors of the form where Algorithm for Solution of ODEs Take
Laplace Transform of both sides of ODE Solve for Y(s)=p(s)/q(s)
Factor the characteristic polynomial q(s) Perform partial fraction
expansion Inverse Laplace using Tables of Laplace Transforms
Slide 83
Transfer Function Models of Dynamical Processe Process Dynamics
and Control
Slide 84
Transfer Function n Heated stirred tank example e.g. e.g. The
block is called the transfer function relating Q(s) to T(s) + + + T
in (s) Q(s) T(0) T(s)
Slide 85
Process Control Time Domain Transfer function Modeling,
Controller Design and Analysis Process Modeling, Experimentation
and Implementation Laplace Domain Ability to understand dynamics in
Laplace and time domains is extremely important in the study of
process control
Slide 86
Transfer function n n Order of underlying ODE is given by
degree of characteristic polynomial e.g. First order processes
Second order processes n n Steady-state value obtained directly
e.g. First order response to unit step function Final value theorem
n n Transfer functions are additive and multiplicative
Slide 87
Transfer function n Effect of many transfer functions on a
variable is additive + + + T in (s) Q(s) T(0) T(s)
Slide 88
Transfer Function n Effect of consecutive processes in series
in multiplicative n Transfer Function U(s) Y 2 (s)Y 1 (s)
Slide 89
Deviation Variables n n To remove dependence on initial
condition e.g. Remove dependency on T(0) Transfer functions express
extent of deviation from a given steady-state n n Procedure Find
steady-state Write steady-state equation Subtract from linear ODE
Define deviation variables and their derivatives if required
Substitute to re-express ODE in terms of deviation variables
Slide 90
Example n Jacketed heated stirred tank Assumptions Assumptions:
Constant hold-up in tank and jacket Constant heat capacities and
densities Incompressible flowModel F, T in F c, T cin F c, T c F, T
h
Slide 91
Nonlinear ODEs Q: If the model of the process is nonlinear, how
do we express it in terms of a transfer function? A: We have to
approximate it by a linear one (i.e.Linearize) in order to take the
Laplace. f(x 0 ) f(x) x x0x0
Slide 92
Nonlinear systems n n First order Taylor series expansion 1.
Function of one variable 2. Function of two variables 3. ODEs
Slide 93
Transfer function n n Procedure to obtain transfer function
from nonlinear process models Find steady-state of process
Linearize about the steady-state Express in terms of deviations
variables about the steady-state Take Laplace transform Isolate
outputs in Laplace domain Express effect of inputs in terms of
transfer functions
Slide 94
First order Processes Examples Examples, Liquid storage h F
FiFi
Slide 95
First Order Processes Examples Examples: Speed of a Car
Stirred-tank heater Note:
Slide 96
First Order Processes Liquid Storage Tank Speed of a car
Stirred-tank heater K p / A/ M/b1/b 1/ C p F V/F First order
processes are characterized by: 1. Their capacity to store
material, momentum and energy 2. The resistance associated with the
flow of mass, momentum or energy in reaching their capacity
Slide 97
First order processes Liquid storage: Capacity to store mass :
A Resistance to flow : 1/ Car: Capacity to store momentum: M
Resistance to momentum transfer : 1/b Stirred-tank heater Capacity
to store energy: C p V Resistance to energy transfer : 1/ C p F
Time Constant = = (Storage capacitance)* (Resistance to flow)
Slide 98
First order process n n Step response of first order process
Step input signal of magnitude M 0.632 y(t)/K p M t/
Slide 99
First order process n What do we look for? Process Gain:
Steady-State Response Process Time Constant: = n What do we need?
Process at steady-state Step input of magnitude M Measure process
gain from new steady-state Measure time constant Time Required to
Reach 63.2% of final value
Slide 100
First order process Ramp response: Ramp input of slope a
00.511.522.533.544.55 0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 a t/ y(t)/K p
a
Slide 101
First order Process Sinusoidal response Sinusoidal input Asin(
t) 02468101214161820 -1.5 -0.5 0 0.5 1 1.5 2 AR y(t)/A t/
Slide 102
First order Processes 10 -2 10 10 0 1 2 -2 10 10 0 AR/K p pp
Bode Plots 10 -2 10 10 0 1 2 -100 -80 -60 -40 -20 0 pp High
Frequency Asymptote Corner Frequency Amplitude RatioPhase
Shift
Slide 103
Integrating Processes Example: Liquid storage tank Process acts
as a pure integrator h F FiFi
Slide 104
Process Modeling n Step input of magnitude M Output Time Input
Time Slope = KM
Slide 105
Integrating processes n Unit impulse response Output Time Input
Time KM
Slide 106
Integrating Processes n Rectangular pulse response Output Time
Input Time
Slide 107
Second Order Processes Three types of second order process: 1.
Multicapacity processes: processes that consist of two or more
capacities in series e.g. Two heated stirred-tanks in series 2.
Inherently second order processes: Fluid or solid mechanic
processes possessing inertia and subjected to some acceleration
e.g. A pneumatic valve 3. Processing system with a controller:
Presence of a controller induces oscillatory behavior e.g. Feedback
control system
Slide 108
Second order Processes n Multicapacity Second Order Processes
Naturally arise from two first order processes in series By
multiplicative property of transfer functions U(s)Y(s) U(s)
Slide 109
Second Order Processes n Inherently second order process: e.g.
Pneumatic Valve Momentum Balance x p
Slide 110
Second order Processes n Second order process: Assume the
general form where P = Process steady-state gain = Process time
constant = Damping Coefficient n Three families of processes
Underdamped =1Critically Damped Overdamped n Note: Chemical
processes are typically overdamped or critically damped
Slide 111
Second Order Processes n n Roots of the characteristic
polynomial Case 1) >1: Two distinct real roots System has an
exponential behavior Case 2) =1:One multiple real root Exponential
behavior Case 3) :Two complex roots System has an oscillatory
behavior
Slide 112
Second order Processes n Step response of magnitude M
012345678910 0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2
Slide 113
Second order process Observations Responses exhibit overshoot
(y(t)/KM >1) when
Slide 114
Second order processes n Example - Two Stirred tanks in series
M T in, w Q T 1, w M Q T 2, w Response of T 2 to T in is an example
of an overdamped second order process
Slide 115
Second order Processes Characteristics of underdamped second
order process 1. Rise time, t r 2. Time to first peak, t p 3.
Settling time, t s 4. Overshoot: 5. Decay ratio:
Slide 116
Second order Processes -5% +5% a b c trtr tsts P tptp
Slide 117
Second Order Process n Sinusoidal Response where
Slide 118
Second Order Processes n Bode Plots =1 =1
Slide 119
More Complicated processes Transfer function typically written
as rational function of polynomials where r(s) and q(s) can be
factored as s.t.
Slide 120
Poles and zeroes Definitions: zeros the roots of r(s) are
called the zeros of G(s) poles the roots of q(s) are called the
poles of G(s) Poles: Directly related to the underlying
differential equation If Re(p i )0 then there is at least one term
of the form e p i t - y(t) does not vanish
Slide 121
Poles e.g. A transfer function of the form withcan factored to
a sum of A constant term from s A e -t/ from the term ( s+1) A
function that includes terms of the form Poles can help us to
describe the qualitative behavior of a complex system (degree>2)
The sign of the poles gives an idea of the stability of the
system
Slide 122
Poles n n Calculation performed easily in MATLAB n n Function
ROOTS e.g. ROOTS([1 1 1 1]) ans = 0.0000 + 1.0000i 0.0000 - 1.0000i
MATLAB
Slide 123
Poles Plotting poles in the complex plane Roots: -1.0, 1.0j,
-1.0j
Slide 124
Poles Process Behavior with purely complex poles
Slide 125
Poles Roots: -0.4368, -0.4066+0.9897j, -0.4066-0.9897j
Slide 126
Poles Process behavior with mixed real and complex poles
Slide 127
Poles Roots: -0.7441, -0.3805+1.0830j, -0.3805-1.0830j,
0.2550
Slide 128
Poles Process behavior with unstable pole
Slide 129
Zeros Transfer function: Let is the dominant time constant
Slide 130
Zeros Observations: Adding a zero to an overdamped second order
process yields overshoot and inverse response Inverse response is
observed when the zeros lie in right half complex plane, Re(z)>0
Overshoot is observed when the zero is dominant () Pole-zero
cancellation yields a first order process behavior In physical
systems, overshoot and inverse response are a result of two process
with different time constants, acting in opposite directions
Slide 131
Zeros Can result from two processes in parallel If gains are of
opposite signs and time constants are different then a right half
plane zero occurs U(s)Y(s)
Slide 132
Dead Time Time required for the fluid to reach the valve
usually approximated as dead time h FiFi Control loop Manipulation
of valve does not lead to immediate change in level
Slide 133
Dead time Delayed transfer functions e.g. First order plus
dead-time Second order plus dead-time U(s) Y(s)
Slide 134
Dead time n Dead time (delay) Most processes will display some
type of lag time Dead time is the moment that lapses between input
changes and process response DD Step response of a first order plus
dead time process
Slide 135
Dead Time n n Problem use of the dead time approximation makes
analysis (poles and zeros) more difficult n n Approximate dead-time
by a rational (polynomial) function Most common is Pade
approximation
Slide 136
Pade Approximations n n In general Pade approximations do not
approximate dead-time very well n n Pade approximations are better
when one approximates a first order plus dead time process n n Pade
approximations introduce inverse response (right half plane zeros)
in the transfer function n n Limited practical use
Slide 137
Process Approximation n Dead time First order plus dead time
model is often used for the approximation of complex processes n
Step response of an overdamped second order process 012345678 0 0.1
0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1 - First Order plus dead time o
Second Order
Slide 138
Process Approximation n Second order overdamped or first order
plus dead time? n Second order process model may be more difficult
to identify -- First order plus dead time - Second order overdamped
o Actual process
Slide 139
Process Approximation n n Transfer Function of a delay system
First order processes Second order processes G(s) Y(s) U(s)
Slide 140
Process Approximation n n More complicated processes Higher
order processes (e.g. N tanks in series) For two dominant time
constants and process well approximated by For one dominant time
constant process well approximated by Y(s) U(s)
Slide 141
Process Approximation n Example
Slide 142
Empirical Modeling Objective: To identify low-order process
dynamics (i.e., first and second order transfer function models)
Estimate process parameters (i.e., K p, and Methodologies: 1. Least
Squares Estimation more systematic statistical approach 2. Process
Reaction Curve Methods quick and easy based on engineering
heuristics
Slide 143
Empirical Modeling Least Squares Estimation: Simplest model
form Process Description where y vector of process measurement
xvector of process inputs 1, 0 process parameters Problem: Find 1,
0 that minimize the sum of squared residuals (SSR)
Slide 144
Empirical Modeling Solution Differentiate SSR with respect to
parameters These are called the normal equations. Solving for
parameters gives: where
Slide 145
Empirical Modeling Compact form Define Then Problem find value
of that minimize SSR
Slide 146
Empirical Modeling Solution in Compact Form Normal Equations
can be written as which can be shown to give or In practice
Manipulations are VERY easy to perform in MATLAB Extends to general
linear model (GLM) Polynomial model
Slide 147
Empirical Modeling Control Implementation: previous technique
applicable to process model that are linear in the parameters (GLM,
polynomials in x, etc) i.e. such that, for all i, the derivatives
are not a function of typical process step responses first order
Nonlinear in K p and overdamped second order Nonlinear in K p, and
nonlinear optimization is required to find the optimum
parameters
Slide 148
Empirical Modeling Nonlinear Least Squares required for control
applications system output is generally discretized or, simply
First Order process (step response) Least squares problem becomes
the minimization of This yields an iterative problem solution best
handled by software packages: SAS, Splus, MATLAB (function
leastsq)
Slide 149
Empirical Modeling Example Nonlinear Least Squares Fit of a
first order process from step response data Model Data
Slide 150
Empirical Modeling Results: Using MATLAB function leastsq
obtained Resulting Fit
Slide 151
Empirical Modeling Approximation using delayed transfer
functions For first order plus delay processes Difficulty
Discontinuity at makes nonlinear least squares difficult to apply
Solution 1. Arbitrarily fix delay or estimate using alternative
methods 2. Estimate remaining parameters 3. Readjust delay repeat
step 2 until best value of SSR is obtained
Slide 152
Empirical Modeling Example 2 Underlying True Process Data
Slide 153
Empirical Modeling Fit of a first order plus dead time Second
order plus dead time
Slide 154
Empirical Modeling Process reaction curve method: based on
approximation of process using first order plus delay model 1. Step
in U is introduced 2. Observe behavior y m (t) 3. Fit a first order
plus dead time model GpGp GcGc GsGs M/s D(s) Y(s) Y m (s) Y * (s)
U(s) Manual Control
Slide 155
Empirical Modeling First order plus dead-time approximations
Estimation of steady-state gain is easy Estimation of time constant
and dead-time is more difficult KM
Slide 156
Empirical Modeling Estimation of time constant and dead-time
from process reaction curves find times at which process reaches
35.3% and 85.3% Estimate t1t1 t2t2
Slide 157
Empirical Process Example For third order process Estimates:
Compare: Least Squares FitReaction Curve
Slide 158
Empirical Modeling Process Reaction Curve Method based on
graphical interpretation very sensitive to process noise use of
step responses is troublesome in normal plant operations frequent
unmeasurable disturbances difficulty to perform instantaneous step
changes maybe impossible for slow processes restricted to first
order models due to reliability quick and easy Least Squares
systematic approach computationally intensive can handle any type
of dynamics and input signals can handle nonlinear control
processes reliable
Slide 159
Feedback Control n Steam heated stirred tank Feedback control
system: Valve is manipulated to increase flow of steam to control
tank temperature Closed-loop process: Controller and process are
interconnected TT TC IP PsPs Condensate Steam F in,T in F,T IP LT
LC
Slide 160
Feedback Control Control Objective: maintain a certain outlet
temperature and tank level Feedback Control: temperature is
measured using a thermocouple level is measured using differential
pressure probes undesirable temperature triggers a change in supply
steam pressure fluctuations in level trigger a change in outlet
flow Note: level and temperature information is measured at outlet
of process/ changes result from inlet flow or temperature
disturbances inlet flow changes MUST affect process before an
adjustment is made
Slide 161
Examples Feedback Control: requires sensors and actuators e.g.
Temperature Control Loop Controller: software component implements
math hardware component provides calibrated signal for actuator
Actuator: physical (with dynamics) process triggered by controller
directly affects process Sensor: monitors some property of system
and transmits signal back to controller T in, F Te ACP M Controller
Tank - + Valve Thermocouple TRTR
Slide 162
Closed-loop Processes n n Study of process dynamics focused on
uncontrolled or Open-loop processes Observe process behavior as a
result of specific input signals n n In process control, we are
concerned with the dynamic behavior of a controlled or Closed-loop
process Controller is dynamic system that interacts with the
process and the process hardware to yield a specific behaviour GpGp
Y(s)U(s) GcGc GmGm GpGp GvGv + - + + controlleractuator process
sensor R(s) Y(s) D(s)
Slide 163
Closed-Loop Transfer Function Block Diagram of Closed-Loop
Process G p (s)- Process Transfer Function G c (s)- Controller
Transfer Function G m (s)- Sensor Transfer Function G v (s)-
Actuator Transfer Function GcGc GmGm GpGp GvGv + - + +
controlleractuator process sensor R(s) Y(s) D(s)
Slide 164
Closed-Loop Transfer Function For control, we need to identify
closed-loop dynamics due to: - Setpoint changesServo -
DisturbancesRegulatory 1. Closed-Loop Servo Response transfer
function relating Y(s) and R(s) when D(s)=0 Isolate Y(s)
Slide 165
Closed-Loop Transfer Function 2. Closed-loop Regulatory
Response Transfer Function relating D(s) to Y(s) at R(s)=0
Isolating Y(s)
Slide 166
Closed-loop Transfer Function 2. Regulatory Response with
Disturbance Dynamics G d (s)Disturbance (or load) transfer function
3. Overall Closed-Loop Transfer Function Regulatory Servo
Slide 167
PID Controllers The acronym PID stands for: P- Proportional I-
Integral D- Derivative PID Controllers: greater than 90% of all
control implementations dates back to the 1930s very well studied
and understood optimal structure for first and second order
processes (given some assumptions) always first choice when
designing a control system PID controller equation:
Slide 168
PID Control PID Control Equation PID Controller Parameters K c
Proportional gain I Integral Time Constant D Derivative Time
Constant u R Controller Bias Proportional Action Integral Action
Derivative Action Controller Bias
Slide 169
PID Control PID Controller Transfer Function or: Note:
numerator of PID transfer function cancels second order dynamics
denominator provides integration to remove possibility of
steady-state errors
Slide 170
PID Control Controller Transfer Function: or, Note: Many
variations of this controller exist Easily implemented in SIMULINK
each mode (or action) of controller is better studied
individually
Slide 171
Proportional Feedback Form: Transfer function: or, Closed-loop
form:
Slide 172
Proportional Feedback Example: Given first order process: for
P-only feedback closed-loop dynamics: Closed-Loop Time
Constant
Slide 173
Proportional Feedback Final response: Note: for zero offset
response we require Possible to eliminate offset with P-only
feedback (requires infinite controller gain) Need different control
action to eliminate offset (integral) Tracking Error Disturbance
rejection
Slide 174
Proportional Feedback Servo dynamics of a first order process
under proportional feedback - increasing controller gain eliminates
off-set KcKc y(t)/KM t/
Slide 175
Proportional Feedback High-order process e.g. second order
underdamped process increasing controller gain reduces offset,
speeds response and increases oscillation y(t)/KM
Slide 176
Proportional Feedback Important points: proportional feedback
does not change the order of the system started with a first order
process closed-loop process also first order order of
characteristic polynomial is invariant under proportional feedback
speed of response of closed-loop process is directly affected by
controller gain increasing controller gain reduces the closed-loop
time constant in general, proportional feedback reduces (does not
eliminate) offset speeds up response for oscillatory processes,
makes closed-loop process more oscillatory
Slide 177
Integral Control Integrator is included to eliminate offset
provides reset action usually added to a proportional controller to
produce a PI controller PID controller with derivative action
turned off PI is the most widely used controller in industry
optimal structure for first order processes PI controller form
Transfer function model
Slide 178
PI Feedback Closed-loop response more complex expression degree
of denominator is increased by one
Slide 179
PI Feedback Example PI control of a first order process
Closed-loop response Note: offset is removed closed-loop is second
order
Slide 180
PI Feedback Example (contd) effect of integral time constant
and controller gain on closed-loop dynamics natural period of
oscillation damping coefficient integral time constant and
controller gain can induce oscillation and change the period of
oscillation
Slide 181
PI Feedback Effect of integral time constant on servo dynamics
y(t)/KM 0.01 0.1 0.5 1.0 K c =1
Slide 182
PI Feedback Effect of controller gain affects speed of response
increasing gain eliminates offset quicker y(t)/KM 0.1 0.5 1.0 5.0
10.0 I =1
Slide 183
PI Feedback Effect of integral action of regulatory response
reducing integral time constant removes effect of disturbances
makes behavior more oscillatory y(t)/KM
Slide 184
PI Feedback Important points: integral action increases order
of the system in closed-loop PI controller has two tuning
parameters that can independently affect speed of response final
response (offset) integral action eliminates offset integral action
should be small compared to proportional action tuned to slowly
eliminate offset can increase or cause oscillation can be
de-stabilizing
Slide 185
Derivative Action Derivative of error signal Used to compensate
for trends in output measure of speed of error signal change
provides predictive or anticipatory action P and I modes only
response to past and current errors Derivative mode has the form if
error is increasing, decrease control action if error is
decreasing, decrease control action Always implemented in PID
form
Slide 186
PID Feedback Transfer Function Closed-loop Transfer Function
Slightly more complicated than PI form
Slide 187
PID Feedback Example: PID Control of a first order process
Closed-loop transfer function
Slide 188
PID Feedback Effect of derivative action on servo dynamics 2.0
1.0 0.5 0.1 y(t)/KM
Slide 189
PID Feedback Effect of derivative action on regulatory response
increasing derivative action reduces impact of disturbances on
control variable slows down servo response and affects oscillation
of process 2.0 1.0 0.5 0.1
Slide 190
Derivative Action Important Points: Characteristic polynomial
is similar to PI derivative action does not increase the order of
the system adding derivative action affects the period of
oscillation of the process good for disturbance rejection poor for
tracking the PID controller has three tuning parameters and can
independently affect, speed of response final response (offset)
servo and regulatory response derivative action should be small
compared to integral action has a stabilizing influence difficult
to use for noisy signals usually modified in practical
implementation
Slide 191
Closed-loop Stability Every control problem involves a
consideration of closed-loop stability General concepts: BIBO
Stability: An (unconstrained) linear system is said to be stable if
the output response is bounded for all bounded inputs. Otherwise it
is unstable. Comments: Stability is much easier to prove than
unstability This is just one type of stability
Slide 192
Closed-loop Stability Closed-loop dynamics if G OL is a
rational function then the closed-loop transfer functions are
rational functions and take the form and factor as G OL
Slide 193
Closed-loop stability General Stability criterion: A
closed-loop feedback control system is stable if and only if all
roots of the characteristic polynomial are negative or have
negative real parts. Otherwise, the system is unstable. Unstable
region is the right half plane of the complex plane. Valid for any
linear systems. Underlying system is almost always nonlinear so
stability holds only locally. Moving away from the point of
linearization may cause instability.
Slide 194
Closed-loop Stability Problem reduces to finding roots of a
polynomial Easy (1990s) way : MATLAB function ROOTS Traditional: 1.
Routh array: l l Test for positivity of roots of a polynomial 2.
Direct substitution l l Complex axis separates stable and unstable
regions l l Find controller gain that yields purely complex roots
3. Root locus diagram l l Vary location of poles as controller gain
is varied l l Of limited use
Slide 195
Closed-loop stability Routh array for a polynomial equation is
where Elements of left column must be positive to have roots with
negative real parts
Slide 196
Example: Routh Array Characteristic polynomial Polynomial
Coefficients Routh Array Closed-loop system is unstable
Slide 197
Direct Substitution n n Technique to find gain value that
de-stabilizes the system. n n Observation: Process becomes unstable
when poles appear on right half plane Find value of K c that yields
purely complex poles n n Strategy: Start with characteristic
polynomial Write characteristic equation: Substitute for complex
pole (s=j ) Solve for K c and
Slide 198
Example: Direct Substitution Characteristic equation
Substitution for s=j Real PartComplex Part System is unstable
if
Slide 199
Root Locus Diagram Old method that consists in plotting poles
of characteristic polynomial as controller gain is changed e.g. K c
-0 1
Slide 200
Stability and Performance n n Given plant model, we assume a
stable closed-loop system can be designed n n Once stability is
achieved - need to consider performance of closed-loop process -
stability is not enough n n All poles of closed-loop transfer
function have negative real parts - can we place these poles to get
a good performance S: Stabilizing Controllers for a given plant P:
Controllers that meet performance S P C Space of all
Controllers
Slide 201
Controller Tuning Can be achieved by Direct synthesis : Specify
servo transfer function required and calculate required controller
- assume plant = model Internal Model Control: Morari et al. (86)
Similar to direct synthesis except that plant and plant model are
concerned Tuning relations: Cohen-Coon - 1/4 decay ratio designs
based on ISE, IAE and ITAE Frequency response techniques Bode
criterion Nyquist criterion Field tuning and re-tuning
Slide 202
Direct Synthesis From closed-loop transfer function Isolate G c
For a desired trajectory (C/R) d and plant model G pm, controller
is given by not necessarily PID form inverse of process model to
yield pole-zero cancellation (often inexact because of process
approximation) used with care with unstable process or processes
with RHP zeroes
Slide 203
Direct Synthesis 1. Perfect Control cannot be achieved,
requires infinite gain 2. Closed-loop process with finite settling
time For 1st order G p, it leads to PI control For 2nd order, get
PID control 3. Processes with delay requires again, 1st order leads
to PI control 2nd order leads to PID control
Slide 204
IMC Controller Tuning Closed-loop transfer function In terms of
implemented controller, G c
Slide 205
IMC Controller Tuning 1. Process model factored into two parts
where contains dead-time and RHP zeros, steady-state gain scaled to
1. 2. Controller where f is the IMC filter based on pole-zero
cancellation not recommended for open-loop unstable processes very
similar to direct synthesis
Slide 206
Example PID Design using IMC and Direct synthesis for the
process Process parameters: K=0.3, IMC Design: K c =6.97, I =34.5,
d =3.93 Filter 2. Direct Synthesis: K c =4.76, I =30 Servo Transfer
function
Slide 207
Example Result: Servo Response IMC and direct synthesis give
roughly same results IMC not as good due to Pade approximation y(t)
t IMC Direct Synthesis
Slide 208
Example Result: Regulatory response Direct synthesis rejects
disturbance more rapidly (marginally) y(t) t IMC Direct
Synthesis
Slide 209
Tuning Relations Process reaction curve method: based on
approximation of process using first order plus delay model 1. Step
in U is introduced 2. Observe behavior y m (t) 3. Fit a first order
plus dead time model GpGp GcGc GsGs 1/s D(s) Y(s) Y m (s) Y * (s)
U(s) Manuel Control
Slide 210
Tuning Relations Process response 4. Obtain tuning from tuning
correlations Ziegler-Nichols Cohen-Coon ISE, IAE or ITAE optimal
tuning relations KM
Slide 211
Ziegler-Nichols Tunings - Note presence of inverse of process
gain in controller gain - Introduction of integral action requires
reduction in controller gain - Increase gain when derivation action
is introduced Example: PI:K c = 10 I =29.97 PID: K c = 13.33 I =18
I =4.5
Slide 212
Example Ziegler-Nichols Tunings: Servo response y(t) t
Slide 213
Example Regulatory Response Z-N tuning Oscillatory with
considerable overshoot Tends to be conservative
Slide 214
Cohen-Coon Tuning Relations Designed to achieve 1/4 decay ratio
fast decrease in amplitude of oscillation Example: PI:K c =10.27 I
=18.54 K c =15.64 I =19.75 d =3.10
Slide 215
Tuning relations Cohen-coon: Servo More aggressive/ Higher
controller gains Undesirable response for most cases
Slide 216
Tuning Relations Cohen-Coon: Regulatory Highly oscillatory Very
aggressive y(t) t
Slide 217
Integral Error Relations 1. Integral of absolute error (IAE) 2.
Integral of squared error (ISE) penalizes large errors 3. Integral
of time-weighted absolute error (ITAE) penalizes errors that
persist ITAE is most conservative ITAE is preferred
Slide 218
ITAE Relations Choose K c, I and d that minimize the ITAE: For
a first order plus dead time model, solve for: Design for Load and
Setpoint changes yield different ITAE optimum
Slide 219
ITAE Relations From table, we get Load Settings: Setpoint
Settings: Example
Slide 220
ITAE Relations Example (contd) Setpoint Settings Load
Settings:
Slide 221
ITAE Relations Servo Response design for load changes yields
large overshoots for set-point changes
Slide 222
ITAE Relations Regulatory response Tuning relations are based G
L =G p Method does not apply to the process Set-point design has a
good performance for this case
Slide 223
Tuning Relations n n In all correlations, controller gain
should be inversely proportional to process gain n n Controller
gain is reduced when derivative action is introduced n n Controller
gain is reduced as increases n n Integral time constant and
derivative constant should increase as increases n n In general, n
n Ziegler-Nichols and Cohen-Coon tuning relations yield aggressive
control with oscillatory response (requires detuning) n n ITAE
provides conservative performance (not aggressive)
Slide 224
CHE 446 Process Dynamics and Control Frequency Response of
Linear Control Systems
Slide 225
First order Process Response to a sinusoidal input signal
Recall: Sinusoidal input Asin( t) yields sinusoidal output
caharacterized by AR and 02468101214161820 -1.5 -0.5 0 0.5 1 1.5 2
AR y(t)/A t/
Slide 226
First order Processes 10 -2 10 10 0 1 2 -2 10 10 0 AR/K p pp
Bode Plots 10 -2 10 10 0 1 2 -100 -80 -60 -40 -20 0 pp High
Frequency Asymptote Corner Frequency Amplitude RatioPhase
Shift
Slide 227
Second Order Process n Sinusoidal Response where
Slide 228
Second Order Processes Bode Plot =1 =1 Amplitude reaches a
maximum at resonance frequency AR
Slide 229
Frequency Response Q: Do we have to take the Laplace inverse to
compute the AR and phase shift of a 1st or 2nd order process? No Q:
Does this generalize to all transfer function models? Yes Study of
transfer function model response to sinusoidal inputs is called
Frequency Domain Response of linear processes.
Slide 230
Frequency Response Some facts for complex number theory: i) For
a complex number: It follows that where such that Re Im w a b
Slide 231
Frequency Response Some facts: ii) Let z=a-bj and w= a+bj then
iii) For a first order process Let s=j such that
Slide 232
Frequency Response Main Result: The response of any linear
process G(s) to a sinusoidal input is a sinusoidal. The amplitude
ratio of the resulting signal is given by the Modulus of the
transfer function model expressed in the frequency domain, G(i ).
The Phase Shift is given by the argument of the transfer function
model in the frequency domain. i.e.
Slide 233
Frequency Response For a general transfer function Frequency
Response summarized by where is the modulus of G(j ) and is the
argument of G(j ) Note: Substitute for s=j in the transfer
function.
Slide 234
Frequency Response The facts: For any linear process we can
calculate the amplitude ratio and phase shift by: i) Letting s=j in
the transfer functionG(s) ii) G(j ) is a complex number. Its
modulus is the amplitude ratio of the process and its argument is
the phase shift. iii) As , the frequency, is varied that G(j )
gives a trace (or a curve) in the complex plane. iv) The effect of
the frequency, , on the process is the frequency response of the
process.
Slide 235
Frequency Response Examples: 1. Pure Capacitive Process
G(s)=1/s 2. Dead Time G(s)=e - s
Slide 236
Frequency Response Examples: 3. n process in series Frequency
response of G(s) therefore
Slide 237
Frequency Response Examples. 4. n first order processes in
series 5. First order plus delay
Slide 238
Frequency Response n n To study frequency response, we use two
types of graphical representations 1. The Bode Plot: Plot of AR vs.
on loglog scale Plot of vs. on semilog scale 2. The Nyquist Plot:
Plot of the trace of G(j ) in the complex plane n n Plots lead to
effective stability criteria and frequency-based design
methods
Slide 239
Bode Plot Pure Capacitive Process
Slide 240
Bode Plot G1G1 G2G2 G3G3 G
Slide 241
Example: Effect of dead-time G=G d GGdGd
Slide 242
Nyquist Plot Plot of G(j ) in the complex plane as is varied
Relation to Bode plot AR is distance of G(j ) for the origin Phase
angle, , is the angle from the Real positive axis Example First
order process (K=1, =1)
Slide 243
Nyquist Plot Dead-time Second Order
Slide 244
Nyquist Plot Third Order Effect of dead-time (second order
process)
Slide 245
Che 446: Process Dynamics and Control Frequency Domain
Controller Design
Slide 246
PI Controller AR
Slide 247
PID Controller AR
Slide 248
Bode Stability Criterion Consider open-loop control system 1.
Introduce sinusoidal input in setpoint (D(s)=0) and observe
sinusoidal output 2. Fix gain such AR=1 and input frequency such
that =-180 3. At same time, connect close the loop and set R(s)=0
Q: What happens if AR>1? GpGp GcGc GsGs D(s) Y(s) Y m (s) R(s)
U(s) Open-loop Response to R(s) + - + +
Slide 249
Bode Stability Criterion A closed-loop system is unstable if
the frequency of the response of the open-loop G OL has an
amplitude ratio greater than one at the critical frequency.
Otherwise it is stable. Strategy: 1. Solve for in 2. Calculate
AR
Slide 250
Bode Stability Criterion To check for stability: 1. Compute
open-loop transfer function 2. Solve for in =- 3. Evaluate AR at 4.
If AR>1 then process is unstable Find ultimate gain: 1. Compute
open-loop transfer function without controller gain 2. Solve for in
=- 3. Evaluate AR at 4. Let
Slide 251
Bode Criterion Consider the transfer function and controller -
Open-loop transfer function - Amplitude ratio and phase shift - At
=1.4128, =- AR=6.746
Slide 252
Ziegler-Nichols Tuning Closed-loop tuning relation With P-only,
vary controller gain until system (initially stable) starts to
oscillate. Frequency of oscillation is c, Ultimate gain, K u, is
1/M where M is the amplitude of the open-loop system Ultimate
Period Ziegler-Nichols Tunings PK u /2 PI K u /2.2 P u /1.2 PIDK u
/1.7 P u /2 P u /8
Slide 253
Nyquist Stability Criterion If N is the number of times that
the Nyquist plot encircles the point (-1,0) in the complex plane in
the clockwise direction, and P is the number of open- loop poles of
G OL that lie in the right-half plane, then Z=N+P is the number of
unstable roots of the closed-loop characteristic equation. Strategy
1. Substitute s=j in G OL (s) 2. Plot G OL (j ) in the complex
plane 3. Count encirclements of (-1,0) in the clockwise
direction
Slide 254
Nyquist Criterion Consider the transfer function and the PI
controller
Slide 255
Stability Considerations n n Control is about stability n n
Considered exponential stability of controlled processes using:
Routh criterion Direct Substitution Root Locus Bode Criterion
(Restriction on phse angle) Nyquist Criterion n n Nyquist is most
general but sometimes difficult to interpret n n Roots, Bode and
Nyquist all in MATLAB n n MAPLE is recommended for some
applications. Polynomial (no dead-time)
Slide 256
CHE 446 Process Dynamics and Control Advanced Control
Techniques: 1. Feedforward Control
Slide 257
Feedforward Control Feedback control systems have the general
form: where U R (s) is an input bias term. n n Feedback controllers
output of process must change before any action is taken
disturbances only compensated after they affect the process GpGp
GcGc GsGs Y(s) Y m (s) R(s) U(s) + + + GDGD GvGv + + D(s) U R
(s)
Slide 258
Feedforward Control n n Assume that D(s) can be measured before
it affects the process effect of disturbance on process can be
described with a model G D (s) Feedforward Control is possible.
Feedback/Feedforward Controller Structure GpGp GcGc GsGs Y(s) Y m
(s) R(s) U(s) + + + GDGD GvGv GfGf + + D(s) Feedforward
Controller
Slide 259
Feedforward Control Heated Stirred Tank Is this control
configuration feedback or feedforward? How can we use the inlet
stream thermocouple to regulate the inlet folow disturbances Will
this become a feedforward or feedback controller? TT TC1 PsPs
Condensate Steam F,T in F,T TT
Slide 260
Feedforward Control A suggestion: How do we design TC2? TT TC1
PsPs Condensate Steam F,T in F,T TC2 + + TT
Slide 261
Feedforward Control The feedforward controller: Transfer
Function Tracking of Y R requires that GpGp Y(s) U(s) + + GDGD GvGv
GfGf + + D(s) U R (s)
Slide 262
Feedforward Control Ideal feedforward controller: Exact
cancellation requires perfect plant and perfect disturbance models.
Feedforward controllers: very sensitive to modeling errors cannot
handle unmeasured disturbances cannot implement setpoint changes
Need feedback control to make control system more robust
Slide 263
Feedforward Control GpGp GcGc GsGs Y(s) Y m (s) R(s) U(s) + + +
GDGD GvGv GfGf + + D(s) What is the impact of G f on the
closed-loop performance of the feedback control system?
Feedback/Feedforward Control
Slide 264
Feedforward Control Regulatory transfer function of
feedforward/feedback loop Perfect control requires that (as above)
Note: Feedforward controllers do not affect closed- loop stability
Feedforward controllers based on plant models can be unrealizable
(dead-time or RHP zeroes) Can be approximated by a lead-lag unit or
pure gain (rare)
Slide 265
Feedforward Control Tuning: In absence of disturbance model
lead-lag approximation may be good K f obtained from open-loop data
1 and 2 from open-loop data from heuristics Trial-and-error
Slide 266
Feedforward Control Example: Plant: Plant Model: Feedback
Design from plant model: IMC PID tunings
Slide 267
Feedforward Control Possible Feedforward controllers: 1. From
plant models: Not realizable 2. Lead-lag unit 3. Feedforward gain
controller:
Slide 268
Feedforward Control For Controller 2 and 3 Some attenuation
observed at first peak Difficult problem because disturbance
dynamic are much faster
Slide 269
Feedforward Control n n Useful in manufacturing environments if
good models are available outdoor temperature dependencies can be
handle by gain feedforward controllers scheduling issues/ supply
requirements can be handled n n Benefits are directly related to
model accuracy rely mainly on feedback control n n Disturbances
with different dynamics always difficult to attenuate with PID may
need advanced feedback control approach (MPC, DMC, QDMC, H 4
-controllers, etc) n n Use process knowledge (and intuition)
Slide 270
CHE 446: Process Dynamics and Control Advanced Control
Techniques 2. Cascade Control
Slide 271
Cascade Control Jacketed Reactor: Conventional Feedback Loop:
operate valve to control steam flow steam flow disturbances must
propagate through entire process to affect output does not take
into account flow measurement TT TC1 PsPs Condensate Steam F,T in
F,T TT FT
Slide 272
Cascade Control Consider cascade control structure: Note: TC1
calculates setpoint cascaded to the flow controller Flow controller
attenuates the effect of steam flow disturbances TT TC1 PsPs
Condensate Steam F,T in F,T TT FT FC
Slide 273
Cascade Control Cascade systems contain two feedback loops:
Primary Loop regulates part of the process having slower dynamics
calculates setpoint for the secondary loop e.g. outlet temperature
controller for the jacketed reactor Secondary Loop regulates part
of process having faster dynamics maintain secondary variable at
the desired target given by primary controller e.g. steam flow
control for the jacketed reactor example
Slide 274
Cascade Control Block Diagram G c2 G p1 G p2 G v2 G m2 G m1 G
c1 D1D1 D2D2 -- + ++ +
Slide 275
Cascade Control Closed-loop transfer function 1. Inner loop 2.
Outer loop Characteristic equation
Slide 276
Cascade Control Stability of closed-loop process is governed by
Example
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Cascade Control Design a cascade controller for the following
system: 1. Primary: 2. Secondary:
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Cascade Control 1. 1. PI controller only Critical frequency
Maximum gain
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AR Bode Plots Cascade Control ln( )
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Cascade Control 2. Cascade Control Secondary loop no critical
frequency gain can be large Let K c2 =10. Primary loop
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Cascade Control Closed-loop stability: Bode Maximum gain K c1
=10.44 Secondary loop stabilizes the primary loop.
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Cascade Control Use cascade when: conventional feedback loop is
too slow at rejecting disturbances secondary measured variable is
available which responds to disturbances has dynamics that are much
faster than those of the primary variable can be affected by the
manipulated variable Implementation tune secondary loop first
operation of two interacting controllers requires more careful
implementation switching on and off
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CHE 446 Process Dynamics and Control Advanced Control
Techniques 3. Dead-time Compensation
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Dead-time Compensation Consider feedback loop: Dead-time has a
de-stabilizing effect on closed- loop system Presence of dead-time
requires detuning of controller Need a way to compensate for
dead-time explicitly GcGc GpGp e-se-s R C D
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Dead-time Compensation Motivation 0.10.750.50.25
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Dead-time Compensation Use plant model to predict deviation
from setpoint Result: Removes the de-stabilizing effect of
dead-time Problem: Cannot compensate for disturbances with just
feedback (possible offset) Need a very good plant model GcGc GpGp
e-se-s R C D G pm
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Dead-time Compensation Closed-loop transfer function
Characteristic Equation becomes Effect of dead-time on closed-loop
stability is removed Controller is tuned to stabilize undelayed
process model No disturbance rejection
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Dead-time Compensation e -0.5s RC D
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Dead-time Compensation Include effect of disturbances using
model predictions Adding this to previous loop gives GcGc GpGp
e-se-s R C D G pm e-se-s + + + - + + + -
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Dead-time Compensation Closed-loop transfer function
Characteristic Equation Effect of dead-time on stability is removed
Disturbance rejection is achieved Controller tuned for undelayed
dynamics Fast Dynamics Slow Dynamics
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Dead-time Compensation e -0.5s RC D + + + - + + + -
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Dead-time Compensation Alternative form Reduces to classical
feedback control system with called a Smith-Predictor GcGc GpGp
e-se-s R C D G pm (1-e - s ) + + + + + -
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Dead-time compensation Smith-Predictor Design 1. Determine
delayed process model 2. Tune controller G c for the undelayed
transfer function model G pm 3. Implement Smith-Predictor as 4.
Perform simulation studies to tune controller and estimate
closed-loop performance over a range of modeling errors (G pm and m
)
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Dead-time Compensation Effect of dead-time estimation errors: e
-0.5s RC D e-se-s + + + - + + + -