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21
CHAPTER 2
DESIGN AND DEVELOPMENT OF LOADED LINE PHASE
SHIFTER FOR WIRELESS APPLICATION
2.1 PREAMBLE
The demand for phased array systems for performing continuous
scanning has created the need for phase shifters capable of providing, smaller
scan angles with fewer blind spots. The loaded line phase shifters are the most
preferred choice for such applications owing to their smaller phase shifting
property with comparatively low insertion loss (Koul and Bhat 1991 b).
Loaded line phase shifters with semiconductor diode control have
been reported in the literature. A p-i-n diode controlled loaded line phase
shifter for L and S band suitable for beam steering array application is
proposed (White 1965). A reduced size 4-bit 90° phase shifter employing
single-section and a 4 bit 360° network employing 45° section as a basic
building block are reported (Opp and Hoffman 1968). A 75° separation
between the loading susceptances is shown to give better performance than
for 90° separation in Voltage Standing Wave Ratio (VSWR), return loss and
phase shift (Yahara 1972). Design figures for different types of phase shifters
including loaded line are reported (Garver 1972). The design equations for a
loaded line phase shifter for arbitrary susceptance spacing and maximum
bandwidth are obtained (Davis 1974). The diode phase shifter circuits
including loaded line phase shifter and the performance of p-i-n diodes and
requirements of a driver are reported (White 1974).
22
The RF performance of micro strip semiconductor phase shifters
operating at S band and Ultra High Frequency (UHF) are described (Burns
et al 1974). A series loaded line S band phase shifter for small phase shifts
(11.25° and 22.5°) has been proposed. A p-i-n diode based 3 bit F-band phase
shifter for high power applications is reported (Swartz et al 1978). Practical
design of C band 4 bit p-i-n phase shifter is presented (Katsumi and Susumu
1979). The design of loaded-line p-i-n diode digital phase shifter circuits for
main line mounted, stub mounted and switchable stub length conditions is
reported. Starting from the p-i-n diode parameters, optimum designs of these
circuits for obtaining minimum insertion loss, maximum bandwidth and
minimum size have been discussed (Bahl and Gupta 1980).
The circuit design procedures for the loaded-line phase shifter are
presented. The effect of losses in the loading elements on the circuit
parameters and the design factors affecting their bandwidth are discussed
(Atwater 1985). The loaded line phase shifter that incorporated both lossy and
imperfectly matched diodes is reported (Manuel 1990).
Simple closed- form expressions for the admittances separated by a
quarter-wavelength transmission line in a loaded line phase shifter are
presented (Bartolucci et al 1995). Single switch configuration of loaded line
phase shifter is reported. This structure exhibited interesting properties,
leading to reduction in size and the number of semiconductor switches
used(Bartolucci 1996). The low cost phase shifters for L-band phased array
antennas is reported. The performance is enhanced by including extra
compensation circuits in biasing networks of the p-i-n diodes that tuned out
the parasitic elements(Nemai 1997).
First, three bits of the four bit hybrid MIC phase shifter are realized
with the loaded line phase shifter with special tuning elements for the fine
tuning of the required phase shift and is reported (Jan 1998). The least
23
significant bit of 5 bit phase shifter is realized with simplified loaded line
configuration for good matching and is reported (Stanimir 2003). The four
bits of a Ku band six bit phase shifter is realized with loaded line phase shifter
with special tuning elements for the fine tuning of the required phase shift and
is described (Wang et al 2007). A loaded line phase shifter with enlarged
phase shift range and bandwidth is presented (Xinyi and Koenraad 2010 a).
2.2 LOADED LINE PHASE SHIFTER
2.2.1 The Structure
Conventional loaded-line phase shifter circuit as shown in
Figure 2.1 consists of two two-state switchable susceptance (jBi) connected in
shunt with a line which has a section of characteristic impedance Z0 and
electrical length , where i=1, 2 refers to the two states of the switches.
Figure 2.1 Loaded line phase shifter
A loaded line phase shifter with single susceptance element is also
possible. But, two susceptance elements separated by quarter wave length
spacing offers, wider bandwidth (Pozar 1998,Koul and Bhat 1991). A
symmetric pair of quarter-wavelength spaced shunt susceptances that are
small (or series reactance) mutually cancels reflections. These features
provide the phase-shifter section a good match in both the control states,
regardless of the susceptance sign or value.
Input Output
Y0
Yi
Yi
24
The shunt capacitance elements lengthen a transmission line
electrically while inductive elements shorten it. Thus, switching from
inductive to capacitive elements produces an increase in electrical length with
a corresponding phase shift. The phase shifts provided by a pair of shunt
susceptance is equal to the normalized susceptance change of one of them.
Each section of a loaded line phase shifter shown in Figure 2.2 (a) and(b
)consists of a /4 transmission line symmetrically loaded at its ends by small
susceptance which are controlled by semiconductor switches such as p-i-n
diodes. Desired phase shift is obtained by changing electrical length of lines
through switching p-i-n diodes.
Figure 2.2(a) Loaded line phase shifter loaded with lumped susceptance
Figure 2.2(b) Loaded line single bit phase shifter with transmission line
and p-i-n diodes
jBn jBn-jBn -jB
25
2.2.2 Design of Loaded Line Phase Shifter
The design of a phase shifter involves the representation of phase
shifter in its equivalent circuit form (Opp and Hoffman 1968) as shown in
Figure 2.3(a)
Figure 2.3 (a) Electrical equivalent (b) Shunt Susceptance arm of loaded
line phase shifter
Figure 2.3(b) shows the shunt susceptance arm of loaded line phase
shifter along with another similar arm at a distance /4, connected through
main transmission line which decides the susceptance B required to produce
the necessary phase shift. The single arm consists of a /4 line with
characteristic impedance Zt, short transmission line of electrical length l,
with characteristic impedance Z0 = 50 and a diode connected in series with
its cathode ground. The /4 line and short transmission line acts as a matching
network to the diode impedances in ON and OFF conditions, with the main
transmission line with characteristic impedance Zc.
The ABCD matrix of the phase shifter shown in Figure 2.1, under
lossless condition, is given by
A B
C D= [P] [Q] [R] (2.1)
'
Yc’
26
where [P] and [R] are the ABCD matrices of the shunt arms of the phase
shifter and is given by
(P) =i
1 0
jB 1 (2.2)
(R) =1 0
jBi 1 (2.3)
where i = (1, 2) representing diode ON/OFF condition and [Q] is the ABCD
matrix of the main transmission line and is given by (Pozar 1998).
[Q] =c
c
cos jZ sin
jsin / Z cos (2.4)
Hence
[P] [Q] [R] =c
c
cos jZ sin1 0 1 0
jsin / Z cosjBi 1 jBi 1= [M1] (2.5)
By performing matrix multiplication,
c i c
1 2
i c i c c i
cos Z B sin jZ sin[M ]
2jB cos jZ B sin jsin / Z cos Z B sin (2.6)
The ABCD parameters of phase shifter circuit shown in Figure 2.3a
is
c
2
c
cos ' jsin '/ Y '[M ]
jY ' sin ' cos ' (2.7)
27
Since Figure 2.3a is an equivalent circuit of Figure 2.1 matrices M1
and M2 are equivalent, and comparing the ABCD parameters
1
c i' cos (cos Z B sin ) (2.8)
1/22
i ic c
c c
B BY' Y 1 2 cot
Y Y (2.9)
From the ABCD parameters, S parameters are obtained as
(Atwater 1985)
m o m o11 22
m m o m o
B Y C ZS S
2A B Y C Z (2.10)
21 12
m m o m o
2S S
2A B Y C Z (2.11)
where Zo = 1/Yo is the characteristics impedance of the circuit into which the
phase shifter is connected, where subscripts m are used on the matrix
elements.
Under input matched condition S11 = 0, and this leads to
m o m oB Y C Z (2.12)
By substituting this in the expression for transmission coefficient
(S21),equation 2.11
21
m m o c i c o
1 1S
A B Y (cos Z B sin ) jZ Y sin ) (2.13)
28
In the input matched lossless case, magnitude of S21 is unity.
Hence,
c i c o(cos Z B sin ) jZ Y sin 1 (2.14)
Thus,
c icos cos Z B sin (2.15)
c osin Z Y sin (2.16)
where is the phase angle of S21
In complex conjugate mode, the phase is switched symmetrically
about 90 by increments of ± / 2 by loading the line with the diode
operating ON and OFF respectively.
The phase shifter is designed to operate in complex conjugate mode
and the phase is switched symmetrically about 90 by increments of ± /2 by
loading the line with the diode operating ON and OFF respectively.
Substituting the value of = 90 ± /2 in equations (2.15) and (2.16) yields
c o
cos2
Z Zsin
(2.17)
i
o
B costan
Y 2cos
2
(2.18)
where Z0 is characteristic impedance of the circuit, = l is electrical length
of the main transmission line and is phase shift.
29
Calculation of Zt and l
A portion of the shunt susceptance of a loaded line phase shifter is
shown in Figure 2.4. When the diode is in ON condition from Figure 2.4a
DON 0SON 0
0 DON
Z jZ tan lZ Z
Z jZ tan l (2.19)
Using quarter wave transmission line Figure 2.5a
2
tin ON
s OFF
ZZ
Z (2.20)
(a) (b)
Figure 2.4 A portion of shunt susceptance of a loaded line phase shifter
with diode a) ON and b)OFF condition
(a) (b)
Figure 2.5 One arm of shunt susceptance of a loaded line phase shifter
with diode a) ON and b) OFF condition
OnOff
30
As the loaded line phase shifter is designed to operate in complex
conjugate mode, the impedance of one arm is (Atwater 1985)
in ON
i
jZ
B (2.21)
where Bi is the susceptance of one arm.
similarly, when diode is in OFF state, from Figure 2.4 b
DOFF 0SOFF 0
0 DOFF
Z jZ tan lZ Z
Z jZ tan l (2.22)
From Figure 2.5b and using the quarter wave transmission line equation,
2
tin OFF
s ON
ZZ
Z (2.23)
in OFF
i
jZ
B (2.24)
By substituting = 90 in Equation (2.18)
i oB Y tan2
(2.25)
By solving equations (2.20), (2.21), (2.23) and (2.24), Zt and l can
be calculated.
All these design parameters and the derived formulae for the
conventional loaded line phase shifters and are listed in Table 2.1.
31
Table 2.1 Design parameter expressions of loaded line phase shifter
Sl.
NoParameter Expression
1. S,ONZ DON 0SON 0
0 DON
Z jZ tan lZ Z
Z jZ tan l
2. S,OFFZ DOFF 0SOFF 0
0 DOFF
Z jZ tan lZ Z
Z jZ tan l
3. ZC
sin
2cos
ocZZ
4. in ,ONZ in ON
i
jZ
B
5. in,OFFZ in ,OFF
i
jZ
B
6. B1ON o
cosB Y tan
2cos
2
7. B2OFF o
cosB Y tan
2cos
2
8. Zt2 2
t in ,ON S,OFFZ Z Z ;2
t in OFF sONz z z
2.2.3 Issues in Loaded Line Phase Shifters
A loaded line phase shifter consists of periodically loaded
reactances separated by a minimum distance of /4 which increases the total
length of the phase shifter. Also, the loading of the reactance are done by
shunt quarter wave transformers which increases the width of the phase
shifters also. As a result of the above, the total size of the phase shifter
32
increases because of the reactive loading of the transmission line, the Q of the
phase shifter increases and hence, the operating bandwidth of the phase shifter
decreases. To circumvent this problem of size, a novel fractal based phase
shifter is attempted. Since, miniaturization of phase shifter becomes an
important issue in the design of wireless RF systems, this thesis addresses the
issue of miniaturization using the concept of KOCH fractal geometry.
2.3 FRACTAL BASED LOADED LINE PHASE SHIFTER
2.3.1 Preamble
Fractals are fragmented space-filling containers used to pack
electrically large features efficiently into small physical areas efficiently.
Among the well known KOCH, Sierpenski, and Minkowski fractals used for
RF applications, KOCH has been an ideal fractal for phase shifter applications
due to its simplicity for analysis and easiness for fabrication. KOCH fractals
are characterized by iteration factor and iteration order. Iteration factor
represents the construction law of fractal geometry, and iteration order depicts
how many iteration processes are to be carried out. Generation law of KOCH
curve facilitates to begin with a specified initiator.
2.3.2 Generation of KOCH Fractal Geometry
As shown in Figure 2.6, the length of the original microstrip line is
l, the length of the microstrip line K1 is 2W+2L/3 (Chen and Wang 2008) and
the length of the microstrip line K2 is 6W+4L/9. If the line width W L/6,
then the length of the KOCH shaped microstrip lines decreases as the iteration
order increases, and also the occupied circuit area of the KOCH curves
decreased as the iteration order increased. Thus, the space filling property is
provided.
33
(a) K0, zeroth iteration order
(b) K1, first iteration order
(c) K2, second iteration order
Figure 2.6 KOCH fractal shaped micro strip lines whose iteration factor
is 1/5
2.3.3 Construction of Single Bit 22.5 KOCH Loaded Line Phase
Shifter
For a straight microstrip line of /4 electrical length, Figure 2.6
shows generation process of a KOCH-shaped microstrip line with iteration
factor of 1/5. The condition that must be satisfied to get a reduced size micro
strip line by applying KOCH fractal curve is as
LineLengthLine Width
6(2.26)
34
KOCH fractals are applied to shunt quarter wave transmission line
and bias line of conventional loaded line phase shifter with 0.2 iteration factor
with iteration order of one. The resulting layout is shown in Figure 2.7.
Figure 2.7 Layout of single bit miniaturized loaded line phase shifter
2.3.4 Equivalent Circuit Model of KOCH based Fractal Loaded Line
Phase Shifter
For the detailed understanding of operation of the KOCH based
fractal loaded line phase shifter, the equivalent circuit analysis is made. The
equivalent circuit of the KOCH based fractal loaded line phase shifter is sub
divided into four smaller sections
i. Transmission line
ii. Diode section
iii. Bias Network
iv. Stub shunt(KOCH fractal)
i. Transmission Line
The 50 transmission line has two end coupled gaps. The layout
and its corresponding equivalent circuit is shown in Figure 2.8 (a).
35
Figure 2.8(a) Equivalent circuit of transmission lines
ii. Diode
The equivalent circuit model of the chosen diode namely
MA4P789-287 p-i-n Diode for OFF and ON condition of the diode are shown
in Figure 2.8(c) and (d) respectively.
Figure 2.8(b) Equivalent circuit of p-i-n diode
Figure 2.8(c) Equivalent circuit of diode OFF condition
36
Figure 2.8(d) Equivalent circuit of diode ON condition
iii. Bias Network
The open circuited quarter wave transmission lines in biasing
network are represented as series LC resonator and the KOCH is represented
in equivalent circuit form.
Figure 2.8(e) Equivalent circuit of Bias network
37
iv. Fractal structure
Figure 2.8(f) Microstrip Bend
Figure 2.8(g) Equivalent circuit of Bend
Figure 2.8 (h) Equivalent circuit of single KOCH fractal
38
The design equations for the equivalent circuit are tabulated in
Table 2.2. Using the design equations, the component values are estimated.
Table 2.2 Design equations for equivalent circuit of transmission lines
Structure Characteristics and Uses Equation
High impedance series
line
Equivalent to series
inductanceoX Z tan( l)
Low impedance series
line
Equivalent to series
inductanceoB Y tan( l)
Quarter wave open
circuit stub
Equivalent to a LC series
Resonator
o
o
ZL
4
2
o
1C
L
The L and C values of micro strip bed are calculated using equation 2.27 and
2.28
L w100 4 4.21 nH / m
h h (2.27)
bend r rC (14 12.5)w / h (1.83 2.25)pF / m
w w
h
(2.28)
The conventional and reduced size KOCH fractal single bit phase
shifters are the basic building blocks of n bit phase shifters. The issues in
single bit phase shifters are limited to practical applicability as they can
provide only fixed beam tilt. In order to get varied beam scanning in the
desired direction, a n-bit phase shifter is required. Hence, a 3 bit phase shifter
design is attempted purposely in this research.
39
2.4 THREE BIT CONVENTIONAL LOADED LINE PHASE
SHIFTER
2.4.1 Structure of 3 Bit Conventional Loaded Line Phase Shifter
Three bit loaded line phase shifter can be constructed by cascading
of 22.5 , 45 and 90 sections of loaded line phase shifters. It can provide 8
different phase shifts from 0 to 157.5 with an increment of 22.5 . The
different phase shift can be obtained by providing bias to the appropriate
phase shifter sections. The line sketch of the conventional 3 bit loaded
line phase shifter showing the three sections in cascaded form is shown in
Figure 2.9.
Figure 2.9 Line Sketch of Conventional 3 bit loaded line phase shifter
2.5 RESULTS AND DISCUSSION
2.5.1 Design and Simulation of Single Bit 22.5 Conventional Loaded
Line Phase Shifter Section for WLAN Application
Specifications
Frequency of operation (f) = 2.45 GHz
Desired Phase shift is ( ) = 22.5
Bandwidth = 80MHz (2.4 - 2.48GHz)
Z0 =50 and = 90
40
For this specification Microwave associates MA4P789-287 p-i-n
diode is selected due to its low series resistance. The ON state impedance of
the diode was calculated as ZDON=1.639+j21.75 and the OFF state
impedance ZDOFF =-j108.22 . Substituting ZDON and ZDOFF in equation
(2.17), the calculated design data are tabulated in Table 2.3.
Table 2.3 Design parameter values of loaded line phase shifter
Sl. No Parameter Values
1. ZC 49
2. Zt 121
3. l 33.5º
4. ZDON 1.6+j22
5. ZDOFF -j108.75
6. ZINON j250
7. ZINOFF -j250
8. BON 0.004mho
9. BOFF -0.004mho
The simulated layout is shown in Figure 2.10 and the simulation is
done using Advanced Design System (ADS).
VSWR
VSWR2VSWR2=vswr(S22)
VSWR
conven225
conven225_1ModelType=RF
V_DCSRC1
Vdc=1.5 V
PIN_diode
PinDiode2
PIN_diode
PinDiode1
TermTerm2
Z=50 Ohm
Num=2
CAPP2
C13
Term
Term1
Z=50 Ohm
Num=1
VSWR
VSWR3VSWR1=vswr(S11)
VSWR
CAPP2
C11
MSUB
MSub1
Rough=0 um
TanD=0.011
T=0.045 mmHu=1.0e+036 um
Cond=1.0E+50
Mur=1
Er=4.6
H=1.6 mm
MSub
DC
DC1
DC
S_Param
SP1
Step=5 MHz
Stop=3 GHz
Start=2 GHz
S-PARAMETERS
Figure 2.10 Simulated layout of single bit 22.5 conventional loaded line
phase shifter
41
Figure 2.11 (a) shows the simulation results of single bit 22.5
conventional loaded line phase shifter. The plot shows the frequency vs. S
parameters for ON and OFF condition of diode. It is observed from the plot
that the insertion loss is less than -1 dB for the chosen frequency band of 2.2-
2.6 GHz and the return loss is less than -15 dB for the same bandwidth
considering the lossy FR-4 substrate with loss tangent 0.011.
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-30
-25
-20
-15
-10
-5
0
S-P
ara
me
ter
(dB
)
Frequency (GHz)
S11
ON
S11
OFF
S21
ON
S21
OFF
Figure 2.11(a) Simulated S parameter of single bit 22.5 conventional
loaded line phase shifter
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
22.5
45.0
67.5
90.0
112.5
135.0
157.5
180.0
Ph
ase
(d
eg
)
Frequency (GHz)
S21
OFF
S21
ON
Figure 2.11(b) Simulated phase plot of single bit 22.5 conventional
loaded line phase shifter
42
Figure 2.11(b) shows the simulated phase plot of single bit 22.5
conventional loaded line phase shifter for on and off condition of the diodes.
The plot shows the phase shift of 23.2 at 2.45 GHz with ± 2 band width of
100MHz from 2.4 to 2.6GHz.
Table 2.4 Simulation results of single bit 22.5 conventional loaded line
phase shifter
Diode
state
S11
(dB)
S21
(dB)
S21
(degrees)
(on phase-off phase)
Simulated DesiredPhase
Error
ON -22.28 -0.85 131.4-23.2 -22.5 -0.7
OFF -27.42 -0.65 154.6
Table 2.4 shows the simulated results of 22.5 conventional loaded
line phase shifter. At the designed frequency of 2.45 GHz the return loss is
less than -22 dB, insertion loss is less than -0.85 dB and the phase error is
0.7 .
2.5.2 Design of single bit 22.5° KOCH Loaded Line Phase Shifter
For the reduced size KOCH Fractal based single bit loaded line
phase shifter, the calculated design parameters are as shown in Table 2.3 for
the same specifications of conventional loaded line 22.5° phase shifter.
2.5.2.1 Simulation of Single Bit 22.5 KOCH Loaded Line Phase shifter
In the KOCH phase shifter layout, blocking capacitors and p-i-n
diodes are added and simulation is done for the ON and OFF condition
of the diodes as shown in Figure 2.12. These capacitors block the DC power
entering into the measuring equipment. The length of the short transmission
lines is tuned to obtain desired phase shift.
43
V_DCSRC1
Vdc=1.5 V
PinDiode2finalkochmergedfinalkochmerged_1ModelType=RF
PinDiode1
C12
TermTerm2
Z=50 OhmNum=2
Term
Term1
Z=50 Ohm
Num=1
S_Param
SP1
Step=5 MHzStop=3 GHz
Start=2 GHz
S-PARAMET ERS
C11
MSUBMSub1
Rough=0 umTanD=0.011
T=0.045 mmHu=1.0e+036 um
Cond=1.0E+50Mur=1Er=4.6
H=1.6 mm
MSub
Figure 2.12 Simulation of single bit 22.5 KOCH loaded line phase shifter
Figure 2.13 (a) shows that the insertion loss is less than -0.88 dB
for a frequency band of 2.2-2.6 GHz and return loss is less than -14 dB for the
same bandwidth for both ON and OFF condition of diode.
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-30
-28
-26
-24
-22
-20
-18
-16
-14
-12
-10
-8
-6
-4
-2
0
S-p
ara
mete
r (
dB
)
Frequency (GHz)
S11
ON
S11
OFF
S21
ON
S21
OFF
Figure 2.13(a) Simulated return loss and insertion loss of single bit 22.5
KOCH loaded line phase shifter
Figure 2.13(b) shows the simulated phase plot of single bit
22.5 KOCH loaded line phase shifter for on and off condition of the diodes.
44
The plot shows that the phase shift of 22.53 at 2.45 GHz with ± 2 band width
of 81.5MHz is achieved.
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
22.5
45.0
67.5
90.0
112.5
135.0
157.5
180.0S
21(d
eg)
Frequency (GHz)
S21
OFF
S21
ON
Figure 2.13(b) Simulated phase plot of single bit 22.5 KOCH loaded line
phase shifter
Table 2.5 shows the simulated results of 22.5 KOCH loaded line
phase shifter. At the designed frequency of 2.45 GHz, the return loss is more
than 21 dB, insertion loss is less than 0.74 dB and the phase error is 0.03 .
Table 2.5 Simulation results of single bit 22.5 KOCH loaded line phase
shifter
Diode
state
S11
(dB)
S21
(dB)
S21
(degrees)
(ON phase-OFF phase)
Simulated Desired Phase Error
ON-
21.31
-
0.743122.8
-22.53 -22.5 -0.03
OFF-
25.91
-
0.628145.4
45
2.5.2.2 Design and simulation of equivalent circuit model of single bit
22.5 KOCH loaded line phase shifter
The equivalent circuit model for the KOCH loaded line phase
shifter is shown in Figure 2.14. The calculated equivalent circuit model
parameters of the KOCH fractal loaded line phase shifter are tabulated in
Table 2.6.
The circuit is simulated with all distributed components that are
represented in terms of their equivalent circuit form. A bias voltage of 1.5 V
is provided for diode ON condition whereas -20V for diode OFF condition.
The equivalent circuit is simulated in ADS Schematic simulator and the
results are shown in Figure 2.15 (a) and 2.15 (b).
Table 2.6 Component values of Equivalent circuit
Sl. No. Parameter Values
1 C1,C6 470pF
2 C3,C7 .32pF
3 C4 5.5pF
4 C8 .13pF
5 C9 .01pF
6 C10 .013pF
7 C11 .015pF
8 C13 .35pF
9 C12 .05pF
10 C16,C18,C20,C22 2.1pF
11 C14 3.3pF
12 L1 .65nH
13 L2 .7nH
14 L3 1.28nH
15 L5,L7,L8,L9,L10,L11,L12 2.1nH
16 L13,L14,L15 2.8nH
46
CC71
C=c4 pF
C
C7C=420 pF
CC51
C=c4 pF
C
C48
C=c4 pF
C
C64
C=c4 pF
CC65
C=c4 pF
CC74
C=c4 pF
C
C73
C=c4 pF
C
C72
C=c4 pF
L
L38
R=
L=l3 nH
L
L26
R=
L=l4 nH
S_Param
SP1
Step=3 MHz
Stop=2.8 GHzStart=2.2 GHz
S-PARAM ETERS
C
C8
C=420 pF
C
C3C=2.4188 pF {t}
L
L40
R=
L=l3 nH
L
L34
R=L=l3 nH
LL35
R=
L=l3 nH
L
L36
R=L=l3 nH
LL37
R=
L=l3 nH
L
L39
R=L=l3 nH
LL41
R=
L=l3 nH
L
L42
R=
L=l3 nH
L
L43
R=L=l3 nH
VAR
VAR1
c4=2.1
l4=2.1
l3=4.05
E q nV a r
L
L24
R=
L=l4 nH
LL25
R=
L=l4 nH
L
L22
R=L=l4 nH
L
L23
R=L=l4 nH
L
L20
R=
L=l4 nH
LL21
R=
L=l4 nHL
L18
R=L=l4 nH
L
L19
R=L=l4 nH
LL27
R=
L=l4 nH
L
L29
R=
L=l4 nH
L
L28
R=
L=l4 nH
LL31
R=
L=l4 nH
L
L30
R=L=l4 nH
L
L33
R=L=l4 nH
L
L32
R=L=l4 nH
C
C24
C=0.05 pF
C
C23C=0.05 pF
C
C20C=0.35 pF
C
C22
C=0.35 pF
V_DC
SRC1Vdc=-20 V
TermTerm2
Z=50 Ohm
Num=2TermTerm1
Z=50 Ohm
Num=1
L
L6
R=
L=26 nH {t}
C
C9C=1.269 pF {-t}
C
C10
C=1.269 pF {-t}
CC6
C=3.32 pF
CC12
C=0.13 pF
C
C13
C=0.1 pF
C
C14C=0.013 pF
C
C16
C=.013 pF
C
C17
C=0.1 pF
L
L12
R=L=0.7 nH
C
C18
C=.013 pF LL14
R=
L=0.7 nH
DCDC1
DC
L
L11
R=L=0.65 nH
L
L13
R=
L=0.65 nH
C
C15C=0.15 pF C
C19
C=0.15 pF
C
C11C=36.50027 pF {t}
C
C2
C=36.50027 pF {t}
Figure 2.14 Equivalent circuit of single bit 22.5 KOCH loaded line phase shifter
Diode
KOCH
Equivalent
Bias
Network
KOCH
Equivalent
Diode
47
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-3.0
-2.5
-2.0
-1.5
-1.0
-0.5
0.0
S2
1(d
B)
Frequency (GHz)
S21
OFF
S21
ON
Figure 2.15(a) Simulated insertion loss of equivalent circuit model of
single bit 22.5 KOCH loaded line phase shifter
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-50
-40
-30
-20
-10
0
S1
1(d
B)
Frequency (GHz)
S11
OFF
S11
ON
Figure 2.15(b) Simulated return loss of equivalent circuit model of single
bit 22.5 KOCH loaded line phase shifter
The OFF state insertion loss is -0.6dB and ON state insertion loss is
about -1.6 dB .The return loss is less than -15 dB for ON state but for OFF
state it ranges from -10 dB to -40dB in the frequency range of 2.4-2.48GHz.
48
2.5.2.3 Fabrication of Single Bit 22.5 KOCH Loaded Line Phase
shifter
To validate the simulation results, a single bit 22.5° KOCH loaded
line phase shifter is fabricated on a FR-4 substrate (thickness of 1.6 mm;
dielectric constant r of 4.6 and loss tangent of 0.011) using a copper etching
process. Two p-i-n diodes (MA4P789-287 with SOT-23 package), capacitors
and SMA connectors are used in the circuit. The p-i-n diodes are ground
through holes by PTH. The phase shifter RF performance is measured using
Agilent ENA series E5062A vector network analyzer. The fabricated single
bit 22.5 KOCH loaded line phase shifter is shown in Figure 2.16.
Figure 2.16 Prototype of single bit 22.5 KOCH loaded line phase shifter
Figure 2.17(a) shows measursed S parameter performance. The
return loss is less than -13 dB for the entire band of 2.4-2.5GHz and insertion
loss ranges from -2.1 to -2.4 dB for ON and OFF condition. Figure 2.17 (b)
shows the measured phase plot of single bit 22.5 KOCH loaded line phase
shifter for ON and OFF condition of the diodes. The plot shows a phase shift
of 22.35 at 2.45 GHz with ±2 band width of 100MHz.
49
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-30
-28
-26
-24
-22
-20
-18
-16
-14
-12
-10
-8
-6
-4
-2
0
S-p
ara
met
er (
dB
)
Frequency (GHz)
S11
ON
S11
OFF
S21
ON
S21
OFF
Figure 2.17(a) Measured return loss and insertion loss of single bit
22.5 KOCH loaded line phase shifter
2.40 2.41 2 .42 2.43 2.44 2.45 2.46 2.47 2 .48 2.49 2.50
-200
-150
-100
-50
0
50
100
150
200
S2
1 (
deg
)
Frequency (G H z)
S21
O N
S21
OFF
Figure 2.17(b) Measured phase of single bit 22.5 KOCH loaded line
phase shifter
50
Table 2.7 Measured results of single bit 22.5 KOCH loaded line phase
shifter at 2.45GHz
Diode
state
S11
(dB)
S21
(dB)
S21
(degrees)
(on phase-off phase)
Simulated DesiredPhase
Error
ON -17.74 -2.206 -75.119-22.35 -22.5 0.15
OFF -21.70 -2.126 -52.765
The Table 2.7 shows the Measured results of 22.5 KOCH loaded
line phase shifter. At the designed frequency 2.45 GHz, the return loss is less
than -17 dB, insertion loss is less than -2.2 dB and the phase error is 0.15 .
2.6 DESIGN OF 3 BIT CONVENTIONAL LOADED LINE
PHASE SHIFTER
Specifications
Frequency of operation (f) = 2.45 GHz
Desired Phase shift ( ) = 22.5 ,45 ,67.5 ,90 ,112.5 ,135 ,157.5
Bandwidth = 80MHz (2.4 - 2.48GHz)
Z0 =50 and = 90
A 3 bit conventional loaded line phase shifter layout for the above
stated specification is designed as per the design parameter stated in Table
2.1.and using ADS(Advanced design suit) software. The layout is shown in
Figure 2.18.
51
Figure 2.18 Layout of 3 bit conventional loaded line phase shifter.
2.7 DESIGN AND SIMULATION OF 3 BIT KOCH LOADED
LINE PHASE SHIFTER
KOCH fractals are applied to shunt quarter wave transmission line
and bias line of different sections (22.5 , 45 and 90 ) of conventional loaded
line Phase shifter layout with 0.2 iteration factor. The iteration order of two is
applied to 22.5 phase shifter section and iteration order of one is applied to
45 and 90 phase shifter sections. Simulation layout of 3 bit KOCH loaded
line Phase shifter is shown in Figure 2.19 .
Figure 2.19 Simulation of 3 bit KOCH loaded line phase shifter
52
2.7.1 Simulation of 3 Bit KOCH Loaded Line Phase Shifter
Figure 2.20(a) shows the simulated performance of return loss. It
shows return loss for all the phase bits are less than -15dB for the desired
frequency band 2.4 – 2.48 GHz.
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50-30
-25
-20
-15
S11
(000)
S11
(001)
S11
(010)
S11
(011)
S11
(100)
S11
(101)
S11
(110)
S11
(111)
S11 (
dB
)
F requency (G H z)
Figure 2.20(a) Simulated return loss of 3 bit KOCH loaded line phase
shifter
2 .40 2 .41 2 .42 2 .43 2 .44 2 .45 2 .46 2 .47 2 .48 2 .49 2 .50-2 .00
-1 .75
-1 .50
S21
(d
B)
F requ ency (G H z)
S2 1
(0 0 0 )
S2 1
(0 0 1 )
S2 1
(0 1 0 )
S2 1
(0 1 1 )
S2 1
(1 0 0 )
S2 1
(1 0 1 )
S2 1
(1 1 0 )
S2 1
(1 1 1 )
Figure 2.20(b) Simulated insertion loss of 3 bit KOCH loaded line phase
shifter
53
Figure 2.20 (b) shows the simulated insertion loss performance of 3
bit KOCH loaded line phase shifter. It shows a variation of insertion loss from
-1.68 dB to -2dB for various phase bits in the desired band of 2.4GHz to
2.48GHz.
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-200
-150
-100
-50
0
50
100
150
200
S2
1 (
deg
)
Frequency (GHz)
S21
(000)
S21
(001)
S21
(010)
S21
(011)
S21
(100)
S21
(101)
S21
(110)
S21
(111)
Figure 2.20 (c) Simulated phase plot of 3 bit KOCH loaded line phase
shifter
Figure 2.20(c) shows the simulated phase performance of 3 bit
KOCH loaded line phase shifter. All the phase bits are linear in the desired
band width of 2.4GHz to 2.48GHz. It also shows that least significant bits
22.5 and 45 bits are linear over 2.2 to 2.8GHz.
Table 2.8 shows the simulated results of 3 bit KOCH loaded line
phase shifter. At the designed frequency of 2.45 GHz, the return loss is more
than 19.5 dB, insertion loss is less than 1.95 dB and a maximum phase error is
1.35 for 111 phase bit.
Phase shift = 126.594 -(-76.779 )=203.373
= 360 -203.373 = 156.627
54
Table 2.8 Simulated results of three bit KOCH loaded line phase shifter
at 2.45 GHz
Bit
InputS11 (dB) S21 (dB)
S21
(degrees)
(ON phase-OFF phase)
Obtained DesiredPhase
Error
000 -23.384 -1.658 -77.243 - - -
001 -26.206 -1.673 -99.733 22.49 22.5 .01
010 -22.129 -1.749 -121.51 44.274 45 0.726
011 -25.048 -1.762 -143.92 66.68 67.5 0.8
100 -19.870 -1.851 -167.31 90.071 90 0.071
101 -21.515 -1.867 170.301 112.45 112.5 0.05
110 -19.551 -1.951 148.965 133.79 135 1.21
111 -23.244 -1.954 126.606 156.15 157.5 1.35
2.7.2 Fabrication and Testing of 3 bit KOCH Loaded Line Phase
Shifter
The simulation results are validated by fabricating the circuits on a
commercially available low cost FR-4 substrate using wet etching process.
The mask necessary for the fabrication is directly generated by the simulator.
Blocking capacitors, p-i-n diodes and SMA connectors are hand soldered.
The RF performance of the fabricated Phase shifter is measured
using Agilent ENA series E5062A Vector network analyzer. The fabricated
prototype of the 3-bit KOCH loaded line phase shifter is shown in
Figure 2.21.
55
Figure 2.21 Fabricated prototype of 3 bit KOCH loaded line phase shifter
2.7.3 Measured Results of 3 Bit KOCH Loaded Line Phase Shifter
Figure 2.22(a) shows the performance of return loss .The return
loss is -10dB for 100 phase bit and less than -10dB for other phase bits in the
band of 2.4 to 2.48GHz.
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-40
-35
-30
-25
-20
-15
-10
S1
1(d
B)
Frequency (GHz)
S11
(000)
S11
(001)
S11
(010)
S11
(011)
S11
(100)
S11
(101)
S11
(110)
S11
(111)
Figure 2.22(a) Measured return loss of 3 bit KOCH loaded line phase
shifter
56
Figure 2.22(b) shows the performance of insertion loss. Minimum
insertion loss for the desired band is -1.45dB for 000 and 001phase bit and
maximum is -3.28 dB for 110 phase bits.
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50-3.5
-3.0
-2.5
-2.0
-1.5
-1.0 S
21(000)
S21
(001)
S21
(010)
S21
(011)
S21
(100)
S21
(101)
S21
(110)
S21
(111)
S21(d
B)
Frequency (GHz)
Figure 2.22(b) Measured Insertion loss of 3 bit KOCH loaded line phase
shifter
Figure 2.22 (c) shows the performance of S21 phase of 3 bit KOCH
loaded line phase shifter. It shows that all the phase bits are linear for the
desired band width 2.4 -2.48 GHz. It is also observed that phase shifts of LSB
phase bits are more linear than that of the MSB phase bits.
Figure 2.22 (d) shows the phase shift performance of 3 bit KOCH
loaded line phase shifter. The ±2 band width is satisfied for all phase bits
except 110 and 111 phase bits. ± 5 band width is satisfied for 110 and 111
phase bit.
57
2.2 2.4 2.6 2.8
-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
22.5
45.0
67.5
90.0
112.5
135.0
157.5
180.0S
21
(d
eg
)
Frequency (GHz)
S21
(000)
S21
(001)
S21
(010)
S21
(011)
S21
(100)
S21
(101)
S21
(110)
S21
(111)
Figure 2.22(c) Measured phase plot of 3 bit KOCH loaded line phase
shifter
2.2 2.3 2.4 2.5 2.6 2.7 2.8-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
22.5
45.0
67.5
90.0
112.5
135.0
157.5
180.0
Ph
ase
sh
ift
(deg
)
Frequency (GHz)
S21
(001)
S21
(010)
S21
(011)
S21
(100)
S21
(101)
S21
(110)
S21
(111)
Figure 2.22(d) Measured phase shift of 3 bit KOCH loaded line phase
shifter
58
Table 2.9 shows the measured values of 3 bit KOCH loaded line
phase shifter at the design frequency of 2.45 GHz. It shows that minimum
phase error is 0.2° for 101 phase bit and maximum phase error is 2.16° for
111 phase bit.
Table 2.9 Measured results of three bit KOCH loaded line phase shifter
at 2.45GHz
Bit
Input
S11
(dB)
S21
(dB)
S21
(deg)
(ON phase-OFF
phase)Phase error
Obtained Desired
000 -21.38 -1.45 39.47 - - -
001 -36.20 -2.14 16.10 -22.37 -22.5 0.87
010 -13 -2.5 -7.46 -46.94 -45 1.94
011 -11.42 -2.62 -29.3 -68.79 -67.5 1.29
100 -10.33 -2.96 -51.96 -91.44 -90 1.44
101 -10.95 -2.95 -73.22 -112.7 112.5 0.2
110 -11.65 -3.12 -93.93 -133.42 -135 1.58
111 -10.09 -2.90 -115.85 -155.34 -157.5 2.16
2.8 RF PERFORMANCE COMPARISON OF SINGLE BIT
CONVENTIONAL AND SINGLE BIT KOCH LOADED LINE
PHASE SHIFTERS
The layout simulation, equivalent circuit model simulation and
measured responses of the single bit KOCH 22.5 phase shifter are depicted in
Figure 2.23(a) and (b). The return loss for all condition ranges from -10 dB to
-45 dB. The variation in return loss is due to substrate parameter ( r, h, tan )
variations. The simulated insertion loss for on and off condition is less than -
0.68dB whereas the measured one is less than -2.4dB. This variation of -1.7 dB in
59
the ON and OFF condition is due to soldering, connector losses, and deviation
in substrate loss between the simulated and practical one.
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-50
-40
-30
-20
-10
0
S1
1(d
B)
Frequency (GHz)
S11
ON(Equivalent circuit model)
S11
OFF(Equivalent circuit model)
S11
ON(Measurement)
S11
OFF(Measurement)
S11
ON(Simulation)
S11
OFF(Simulation)
Figure 2.23(a) Simulated, equivalent circuit model and measured return
loss of single bit 22.5 KOCH loaded line phase shifter
2.40 2.42 2.44 2.46 2.48 2.50
-5
-4
-3
-2
-1
0
S2
1(d
B)
Frequency (GHz)
S21
ON(simulation)
S21
OFF(Simulation)
S21
ON(Maesurement)
S21
OFF(Measurement)
S_21offeqS21
ON(Equivqlent circuit model)
S_21offeqS21
OFF(Equivqlent circuit model)
Figure 2.23(b) Simulated, equivalent circuit model and measured
insertion loss of single bit 22.5 KOCH loaded line phase
shifter
60
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-33.75
-22.50
-11.25
0.00
Ph
ase
sh
ift
(deg
)
Frequency (GHz)
Equivqlent circuit model
Measurement
Simulation
Figure 2.23(c) Comparison of Phase shift of single bit KOCH 22.5 phase
shifter
The phase shift performance of layout simulation, equivalent circuit
model and measured ones are compared in Figure 2.22(c). The performances
are within the tolerance range of ±2 in the desired band of 2.4 to 2.48 GHz.
2.9 RF PERFORMANCE OF 3 BIT KOCH LOADED LINE
PHASE SHIFTERS
Figure 2.24(a) and (b) shows the comparison between simulated
and measured performance of return and insertion losses respectively. The
simulated return loss varied between -15dB and -30dB for all eight states
where as the measured one varied between -10dB and -15dB except two LSB
states. This is due to parameter variation of the substrate between simulated
and actual values. The simulated insertion loss varied between -1.5dB and -
2dB where as measured ones varied between -1.5dB and -3.25dB. This is due
to tangent loss variation between the values used in simulation and actual
values and radiation losses.
61
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-40
-30
-20
-10
S1
1(d
B)
Frequency (GHz)
000_Simulated
001_Simulated
010_Simulated
100_Simulated
111_Simulated
000_Measured
001_Measured
010_Measured
100_Measured
111_Measured
Figure 2.24(a) Simulated and measured return loss of the 8 states of
3 bit KOCH loaded line phase shifter
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-3.5
-3.0
-2.5
-2.0
-1.5
-1.0
S21(d
B)
Frequency (GHz)
000_Simulated
001_Simulated
010_Simulated
100_Simulated
111_Simulated
000_Measured
001_Measured
010_Measured
100_Measured
111_Measured
Figure 2.24(b) Simulated and measured insertion loss of the 8 states of 3
bit KOCH loaded line phase shifter
62
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
Ph
ase
sh
ift
(deg
)
Frequency (GHz)
Simulation
Measurement
Figure 2.24(c) Simulated and measured phase shift of the 8 states of 3
bit KOCH loaded line phase shifter
Comparison of simulated and measured phase shift values of 3 bit
KOCH loaded line phase shifter for the desired band 2.4 to 2.48 GHz is shown in
Figure 2.24 (c).The plot shows that there is good agreement between the two.
Simulated and measured phase errors for KOCH phase shifter are minimal.
2.40 2.41 2.42 2.43 2.44 2.45 2.46 2.47 2.48 2.49 2.50
-180.0
-157.5
-135.0
-112.5
-90.0
-67.5
-45.0
-22.5
0.0
Ph
ase
sh
ift
(deg
)
Frequency (GHz)
Koch
Conventional
Figure 2.25 Measured phase shift comparison between KOCH and
conventional loaded line phase shifter for all the 8 states
63
Figure 2.25 shows that the KOCH phase shifter performance is
better than the conventional one in all the phase states.
Figure 2.26 Comparison of Conventional and KOCH three bit loaded
line phase shifters
By applying KOCH, the electrical length in the transverse direction
is reduced. Thus, a miniaturization of 41.88% for single bit and 44% for 3-bit
phase shifter shown in Figure 2.26 is achieved. By using KOCH, a Band
width increase of 19.75 MHz achieved for single bit 22.5 phase bit.
The lower phase bits like 22.5 and 45 are generally realized with
loaded line phase shifter because it offers low insertion loss for these phase
bits. The lower phase bits are investigated for the band 2.3-2.8 GHz to find
out the phase error bandwidth and return loss bandwidth simultaneously
(Xinyi and Koenraad 2010 b). The bandwidth is calculated for ±2 phase error
and -10dB return loss for 22.5 phase bit and 45 phase bit of 3 bit
conventional and KOCH phase shifter.
64
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-6
-5
-4
-3
-2
-1
0
1
2
3
Phase Error
Return Loss
Frequency (GHz)
Ph
ase
Err
or
(deg
)
-40
-35
-30
-25
-20
-15
-10
-5
0
S11
(dB
)
Figure 2.27(a) Relationship between phase error, return loss and
frequency of 22.5° phase bit for conventional three bit
phase shifter
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-8
-6
-4
-2
0
2
4
Phase Error
Return Loss
Frequency (GHz)
Ph
ase
Err
or
(deg
)
-40
-35
-30
-25
-20
-15
-10
-5
0
S11(d
B)
Figure 2.27(b) Relationship between phase error, return loss and
frequency of 22.5° phase bit for KOCH three bit phase
shifter
65
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-16
-14
-12
-10
-8
-6
-4
-2
0
2
4
Phase Error
Return Loss
Frequency (GHz)
Ph
ase
Err
or
(deg
)
-30
-25
-20
-15
-10
-5
0
S11
(dB
)
Figure 2.27(c) Relationship between phase error, return loss and
frequency for 45° phase bit of conventional three bit
phase shifter
2.2 2.3 2.4 2.5 2.6 2.7 2.8
-16
-14
-12
-10
-8
-6
-4
-2
0
2
4
Phase Error
return Loss
Frequency (GHz)
Ph
ase
Err
or
(deg
)
-30
-25
-20
-15
-10
-5
0
S11
(dB
)
Figure 2.27(d) Relationship between phase error, return loss and
frequency of 45° phase bit for KOCH three bit phase
shifter
66
From Figure 2.27(a), (b), (c) and (d) the bandwidth is calculated
and tabulated in Table 2.10.
Table 2.10 Bandwidth comparison of conventional and KOCH 22.5º
and 45º phase bits of 3 Bit loaded line phase shifter
Phase Bit
(in degrees)
Band width (MHz)
Conventional KOCH % increased
22.5 300 348 16
45 180 203 12.8
2.10 CONCLUSION
In this chapter the issue of miniaturization has been addressed using
the concept of fractal geometry. To start with single bit KOCH fractal based
loaded line phase shifter is designed and developed. The simulation results at
2.45GHz show an insertion of - 0.743dB, return loss of -21.3dB and a phase
error of -0.03°.The measured results at 2.45GHz show an insertion loss of -
2.2dB, return loss of -21.7 dB and a phase error 0.15°.While comparing the
simulation and measurement results the return loss remains same in both the
cases.The increase in insertion loss and phase error may be due to loss
tangent variation of dielectric material used.
Next a the 3 bit KOCH fractal based loaded line phase shifter is
designed and developed. The simulation results at 2.45GHz show an average
insertion loss of -1.81 dB for all the 8 phase states. A worst case return loss of
-19.55dB and maximum phase error of -1.35° when all diodes are in ON state.
The measured results show an average insertion loss of -2.58 dB , a worst
case return loss of -10.09dB and a phase error of 2.16° when all diodes are in
ON state. The deviation in the insertion loss and phase error is due to loss
67
tangent variation of the FR-4 substrate and variation in the return loss may be
due to discontinuities arising out of the manufacturing tolerances. However
the RF performance of the 3 bit KOCH loaded line phase shifter is found to
be feasible for the WLAN applications.
KOCH fractal based 3 bit loaded line phase shifter offers a size
reduction of 44%(miniaturization) and band width increment of 16% and
12.8% for 22.5° and 45° phase bits respectively. It is observed that the size
reduction (miniaturization)has been achieved without sacrificing the RF
performance 3 bit KOCH fractal based loaded line phase shifter.