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A. Yener, WCAN@Penn State 1
Performance Enhancement of CDMA Systems Using SmartAntennas: Joint temporal-spatial designs
Aylin Yener
The Pennsylvania State University
March 2, 2004
A. Yener, WCAN@Penn State 2
Motivation for Using Smart Antennas
� The demand for wireless communications is ever growing.
– Each user requests higher data rates and reliability
– More users requests request service simultaneously
� Bandwidth is limited!
� Radio channel is not particularly ’friendly’
– Reflections results in signal arriving at the receiver via multiple paths with random phase
and amplitude
– Arrival of multiple paths introduce delay spread, intersymbol interference
– Significant problems arise from other users interfering with the signal transmission
A. Yener, WCAN@Penn State 3
How can Smart Antennas help?
� Antenna arrays at the receiver:
– M-fold gain for M-antenna elements
– Diversity gain against multipath fading
� Depends on correlation of the fading
– Interference mitigation
� Separation of users with antenna arrays whose radiation pattern is not isotropic
A. Yener, WCAN@Penn State 4
Diversity
� Spatial Diversity
– If the angle spread is large, then small separation of antennas (λ�4) is sufficient for low
correlation
– Handsets, indoor base stations, urban area base stations typically have large angle spread
– High towers may need a lot more antenna spacing ( 10λ) for low correlation
� Polarization Diversity
– Limited gain
� Angle Diversity
– Adjacent narrow beams used
– Small separation sufficient
� Diversity gain at the base station typically achieved by
– Selection Diversity (select the antenna with best quality)
– Maximum ratio combining (weighted sum of signals to max SNR)
A. Yener, WCAN@Penn State 5
Smart Antennas and Interference Suppression
� Current cellular systems: 3 sector antennas, non-interfering channels
� Channel management becomes difficult (too many hand-offs) with too many sectors
� Multibeam antennas (multiple fixed beams) can cover each sector: No handoffs between
beams, limited diversity, limited interference reduction
� Adaptive Arrays
– Combine the signals received at each array element in a way to improve the performance
for the signal of each user, e.g., max SIR
– Effective interference suppression
– M antennas can null out M-1 interferers, can significantly reduce interference even when
there are more than M interferers
– A vehicle to provide multiple access capability for a narrow band system: SDMA
A. Yener, WCAN@Penn State 6
Array Combining (Beamforming)
� Suppress interferer’s by adjusting the weights with which the signals are combined
� Changes in the channel/interference structure can be tracked with adaptive methods
� More complex than multibeam antennas sinceeach userneeds a different combiner
� Typically for narrowband systems, if delay spread is non-negligible; temporal equalization is
needed
� For wideband systems, i.e., CDMA, a combiner for multiple paths is used
� Adaptive arrays are used in
– GSM and IS-136 systems along with temporal equalization
– IS-95 systems along with RAKE receiver
� The temporal and array combining is done in cascade, each optimized for thecorresponding domain
A. Yener, WCAN@Penn State 7
Beamforming (Spatial Filtering)
sgn
sgn
..
.
..
.
sgn bi^
bi^
r(t)
. . .
r (t)1
ia (t)
user i
j
user j
a (t)
r1
r2
rK
. . .
STATIONBASE
r
b
b
k
j
^
^
wi
wk
wj
Ti= sgn (w r)
r (t)
r (t)
2
K
Matched
Temporal
Filter
A. Yener, WCAN@Penn State 8
Frequency
FDMA
K2 user
user
user
1
Division
T
B
Multiple AccessCode
CDMA
1
Division
ACCESS
T
. . .
. . .
. . .
B
METHODSMULTIPLE
frequency, f
time,
t
user
2user
T
B
B
KuserT
B
T
Time
�������������� ������������
��������������
������
������
�������
�������
������
������
�������
�������
������
������
�������
�������
������������
K
2
1
user
TDMA
user
Multiple AccessDivision
user
��
��
��
��
��
��
�������
�������
AccessMultiple
A. Yener, WCAN@Penn State 9
Code Division Multiple Access: Principles
N = (bandwidthexpansionfactor)
one bit interval
t
t
one chip intervalTc
-1
Tb
Processing gain: N(signature
i
of user ibit stream
=-1=+1
signal transmitted by user i
in one bit interval =
p
sequenceof user i)
t
si(t)
+1i
b s(t)i i
b
bT /Tc
bi
ip
A. Yener, WCAN@Penn State 10
Interference Management for CDMA� CDMA systems areinterferencelimited because
– Users haveunique, butnon-orthogonalsignatures
� Strong users can destroy weak user’s communication� near-far problem
� Interference Managementis needed!
BASESTATION
s (t)i
user j
user ijs (t)
t
t
A. Yener, WCAN@Penn State 11
Interference Management Techniques
� Power Control[Zander] [Yates] [Hanly]
� Multiuser Detection (Temporal Filtering)[Verdu][Xie et. al.][Madhow,Honig]
� Beamforming (Spatial Filtering)[Naguib et. al.]
� Power ControlandMultiuser Detection[Ulukus, Yates]
� Power ControlandBeamforming[Rashid-Farrokhi et. al.]
� Multiuser DetectionandBeamforming[Yener, Yates, Ulukus]
� Power Control, Multiuser Detection, andBeamforming[Yener, Yates, Ulukus]
� Power ControlandAdaptive cell sectorization[Saraydar,Yener]
A. Yener, WCAN@Penn State 12
Beamforming (Spatial Filtering)
sgn
sgn
..
.
..
.
sgn bi^
bi^
r(t)
. . .
r (t)1
ia (t)
user i
j
user j
a (t)
r1
r2
rK
. . .
STATIONBASE
r
b
b
k
j
^
^
wi
wk
wj
Ti= sgn (w r)
r (t)
r (t)
2
K
Matched
Temporal
Filter
� More intelligent filters in spatial domain
A. Yener, WCAN@Penn State 13
Linear Multiuser Detection (Temporal Filtering)
..
.
..
.
sgn
sgnBASESTATION
Tc
r(t)
bi^
bi^ T
i= sgn (c r)
s (t)j
user j b
k
j
^
^
Chip MFr-
c i
c j
kc bsgn
user i
s (t)i
� More intelligent filters in temporal domain
A. Yener, WCAN@Penn State 14
Temporal and Spatial Filtering
r(t)
. . .
r (t)1
r sgn
sgn
..
.
..
.
sgns (t)
j ja (t)
user j
bi^
ia (t)
user i
is (t)
rXi
Xk
Xj
= sgn(tr(X R))^biT
i
STATIONBASE
r (t)
r (t)
2
K
Chip sample
2 b
b
k
j
^
^Chip samplerK
Chip sample
1
R
R and X are matrices !
� More intelligent filters in both domains
A. Yener, WCAN@Penn State 15
Temporal-Spatial Filtering
� Several possible filter structures:
– Single userapproach: Temporal-spatial matched filter [Naquib et. al]
– Single user – multiuserapproach: Temporal matched filter + Spatial MMSE or vice versa
[Honig et. al] [Rashid-Farrokhi et. al]
– Cascadedstructures: MMSE temporal combiners cascaded with an MMSE spatial
combiner, or vice versa [Yener, Yates, Ulukus]
� Each of these filters can be expressed as a matrix filter.
� Joint optimum temporal-spatial filter perform better than any cascade structure[Yener et.al.]
� We focus on joint temporal-spatial MMSE filter designs.
A. Yener, WCAN@Penn State 16
Previous work
� Assume synchronous users; single path. Received signal matrix over one bit period:
R �
K
∑k�1
�
PkbkskaTk �N
� E�N�
klNmn� � σ2δkmδln
� Decision statistic computed via linear matrix filterX i
yi �
N
∑n�1
M
∑m�1
�Xi��
nmRnm � tr�XHi R�
� Design matrix filters to minimize the MSE
Xi � arg minX
E
���tr�XHR��bi
��2�
A. Yener, WCAN@Penn State 17
Received Signal
MFCHIP R [ n,1 ]
MFCHIP R [ n,M ]
t = n T
t = n T
c
c
.
.
.
.
.
.
Synchronous system with processing gainN, M antenna elements andK users
A. Yener, WCAN@Penn State 18
Optimum Temporal-Spatial Filter (OTSF)
� Find the matrix filterX i that yields the minimum MSE betweenyi andbi.
xi ��
Pi
�
K
∑k�1
PkqkqHk �σ2I
��1
qi
whereskaTk � qk
� This filter results in the minimum MSE overall possiblefiltering schemes in temporal and
spatial domains
� Resulting jointoptimum filter has a closed form
� Complexity due to the inversion of aNM�NM matrix� Find a simpler receiver structure
� MN could be large! (e.g.N � 64,M � 4)
A. Yener, WCAN@Penn State 19
OTSF Receiver for Useri
r (t)1
Chipsample
Chipsample
Chipsample
r
rc i1
. . .r (t)
r (t)
2
K
2
rK
1
wic i2
c iK
r (t)1
Chipsample
Chipsample
Chipsample
r
r
. . .
r (t)
r (t)
2
K
2
rK
1
Xi
A. Yener, WCAN@Penn State 20
Constrained Temporal-Spatial Filters (CTSF)[Yener et.al.]
� Separable temporal-spatial filters for reduced complexity:Xi � ciw�
i
� Decision statistic for useri:
yi � tr�wic�i R� � c�i Rwi
� Find the separable filters that arejointly optimumin MSE sense
� Rank-1 filters: Constrain the feasible set of possible matrix filters to ones of the form
Xi � ciwTi
– The sameN dimensional temporal filter,ci at the output of each antenna
– Combine the outputs via theM dimensional beamformer,w i
– Jointly optimumci andwi are found iteratively. Rank-1 filters work well when
� system is not overloaded
� reasonably good power control
A. Yener, WCAN@Penn State 21
OTSF vs. CTSF Receiver for Useri
r (t)1
Chipsample
Chipsample
Chipsample
r
rr (t)1
Chipsample
Chipsample
Chipsample
r
rc i1
. . .
. . .r (t)
r (t)
2
K
2
rK
ci
ci
ci
1
wir (t)
r (t)
2
K
2
rK
1
wic i2
c iK
OTSF CTSF
� CTSF:First combine all the chip vectors usingci then combine the resulting vector usingwi
A. Yener, WCAN@Penn State 22
Motivation for Rank-r Filters[Filiz, Yener]
� Rank-1 constrained filters:
– Suboptimal performance due to the constrained solution space
– Performance difference can be pronounced in heavily loaded systems
*Filters with performance between OTSF and the rank-1 constrained filter are needed
� Multipath environments:Need to take advantage of temporal diversity.
� Adaptive Implementation
– Suitable for a cellular environment
– Only the knowledge of training bits is required
*Algorithms that do not require the explicit channel estimates are desirable
A. Yener, WCAN@Penn State 23
Multipath Channel Model
� Transmitted signal of userk
zk�t� ��
Pk
∞
∑n��∞
bk�n�sk�t�nTs�
� Multipath channel impulse response
hk�t� �
L
∑l�1
hk�l δ�t� τk�l�
� Received signal at the output of the antenna array
r�t� �
K
∑k�1
L
∑l�1
hk�l zk�t� τk�l �νk�ak�l �n�t�
A. Yener, WCAN@Penn State 24
Simplified Multipath Channel Model� Synchronous users
� Each user hasL paths with chip synchronous delays
� τk�l �� T such that ISI can be ignored
� Received signal over the observation interval
R �
K
∑k�1
�
PkbkSkHkATk �N
Sk �
�
sk�1� 0. . .
... sk�1�
sk�N�
.... . .
0 sk�N��
�
Hk �
�hk�1 0
...
0 hk�L
� � Ak � �ak�1� � ak�L�
A. Yener, WCAN@Penn State 25
Rank-r Constrained Filters� Achieve the performance improvement by relaxing the constraint:
Xi �argminX
E
���tr�XHR
��bi
��2�
s.t. rank�X� r� 1 r min�N �L�1�M�
� Satisfy the rank constraint by decomposingX i as:
Xi �
r
∑j�1
ci jwTi j
� The MSE and the optimization problem expressions become:
MSE � E
������
r
∑j�1
cHi jRw�
i j�bi
�����
2
��
�ci1� � � � � cir� wi1� � � � � wir� � arg minci1�����cir �wi1�����wir
E
������
r
∑j�1
cHi jRw�
i j�bi
�����
2
��
A. Yener, WCAN@Penn State 26
Receiver Structure
Chip MatchedFiltering r
1
Chip MatchedFiltering
rM
. . . .
]Mr, ... ,1r[=R
c w1 1
T
c wTr r
yi
. . . .
A. Yener, WCAN@Penn State 27
Performance Metric
� MSE expression becomes:
MSE�
r
∑l�1
r
∑j�1
K
∑k�1
PkcHil Vkw�
ilwTi jV
Hk ci j
�σ2r
∑l�1
r
∑j�1
�cH
il ci j
��
wHil wi j
��2
�
Pi
r
∑j�1
ℜ
�
cHi jViw�
i j
��1
whereVk � SkHkATk
� Note that MSE is a function of 2r variables
�ci1� � � � �cir�wi1� � � � �wir�
� MSE is not jointly convex in all variables
� MSE is convex for a single variable, given that the other 2r�1 variables are fixed
� Use alternating minimization algorithm to iteratively minimize the MSE
A. Yener, WCAN@Penn State 28
Alternating Minimization Algorithm
� Each step consists of 2r sub-steps
� At each sub-step, update a single variable to minimize the MSE
� The algorithm can be expressed as
FOR t � 1 : S
FOR x � 1 : r
cix � MMSE��ci j� j ��x��wi j�rj�1�
wix � MMSE��ci j�rj�1��wi j� j ��x�
END
END
wherecix andwix denote the values that minimize MSE
S is the total number of steps
A. Yener, WCAN@Penn State 29
Adaptive Implementation� All users’ parameters needed in deterministic iterations.
� Adaptive implementation is needed in practice.
� Combination of alternating minimization with LMS
– Keep the main structure of the alternating minimization algorithm
– Solve each sub-step using the classical LMS approach
� The classical LMS rule:
wi�n�1� � wi�n��µ�di�n�� yi�n���u�n�
� Define the desired response, decision statistic and the input signal
di � bi�r
∑j ��x
cHi jRw�
i j
yi � cHixRw�
ix
u�n� � Rw�
ix �or RT c�ix�
A. Yener, WCAN@Penn State 30
Parameters that Affect Convergence
� Block sizeB
– LMS converges to optimum in infinite iterations (training bits)
– At each sub-step we truncate the LMS afterB training bits
– SmallerB � premature jumping to the next step
– LargerB � slower overall algorithm
� Step sizeµ
– Smallerµ � slower convergence but higher accuracy
– Largerµ � faster convergence but more residual error
A. Yener, WCAN@Penn State 31
Numerical Results
� A single cell CDMA system with
� N � 16 processing gain
� Linear antenna array withM � 8 elements, equispaced atλ�2
� Channel coefficients are zero mean complex Gaussian variables, normalized such that
E� hk�l 2� � 1
� SNR of desired user is 10 dB
A. Yener, WCAN@Penn State 32
MSE v.s The Iteration Index (K � 40, N � 16, M � 8, L � 3)
5 10 15 20 250
0.2
0.4
0.6
0.8
1
Iteration Index
MS
E
rank−1rank−2rank−4OTSF
A. Yener, WCAN@Penn State 33
SIR v.s The Iteration Index (K � 40, N � 16, M � 8, L � 3)
5 10 15 20 25−20
−15
−10
−5
0
5
10
15
Iteration Index
SIR
(dB
)
OTSFrank−4rank−2rank−1
A. Yener, WCAN@Penn State 34
SIR v.s The Iteration Index (K � 10, N � 16, M � 8, L � 3)
5 10 15 20 25−20
−15
−10
−5
0
5
10
15
Iteration Index
SIR
(dB
)
OTSFrank−4rank−2rank−1
A. Yener, WCAN@Penn State 35
SIR v.s The Number of Paths (K � 40, N � 16, M � 8)
1 2 3 4 5 62
4
6
8
10
12
14
16
Number of Paths
max
SIR
(dB
)
OTSFrank−4rank−2
A. Yener, WCAN@Penn State 36
SIR v.s The Training Bits (K � 40, N � 16, M � 8, L � 3, µ � 0�01)
200 400 600 800 1000 1200 1400 1600 1800 2000−25
−20
−15
−10
−5
0
5
10
Training Bits
SIR
(dB
)
rank−4rank−2rank−1
A. Yener, WCAN@Penn State 37
SIR v.s The Training Bits (K � 40, N � 16, M � 8, L � 3, rank�X� � 2)
200 400 600 800 1000 1200 1400 1600 1800 20000.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1
Training Bits
MS
E
µ = 0.05
µ = 0.01
A. Yener, WCAN@Penn State 38
SIR v.s The Training Bits (K � 40, N � 16, M � 8, µ � 0�01, rank�X� � 4)
200 400 600 800 1000 1200 1400 1600 1800 2000−20
−15
−10
−5
0
5
10
15
Training Bits
SIR
(dB
)
L = 1
L = 3
L = 5
A. Yener, WCAN@Penn State 39
Conclusions
� Smart antennas provide additional wireless capacity
� Joint temporal-spatial multiuser detectors improve the performance of CDMA systems
� Rank constrained filters
– Relaxing the constraint increases the performance
– Near optimal performance can be achieved with a mild increase in complexity
– Trade-off between complexity and performance
� Adaptive implementations
– Only the training bits and the timing of the first path of the desired user are required
– B andµ affect convergence speed and the residual error
� The existence of multipath provides diversity
A. Yener, WCAN@Penn State 40
Further Reading, Current Research
� References
– J. Winters, “Smart Antennas for Wireless Systems”, IEEE Personal Communications,
Feb 1998
– A. Paulraj, C. Papadias, “Space-Time Processing for Wireless Communications”, IEEE
Signal Processing Magazine, November 1997
– J. Liberti, T. Rappaport, Smart Antennas for Wireless Communications, Prentice-Hall,
1999
� Transmitter design issues for multiple antenna systems (narrowband)
� Transmit beamformer design for CDMA systems with receiver antenna arrays
Seehttp://labs.ee.psu.edu/labs/wcanfor papers and the copy of this talk