A Low-Profile Unidirectional Printed Antenna for

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This article has been accepted for publication in a future issue of this journal, but has not been fully edited. Content may change prior to final publication. Citation information: DOI10.1109/TAP.2014.2298246, IEEE Transactions on Antennas and Propagation

IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. AA, NO. B Nov. 2013

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Abstract—By combining a printed reflector-backed one-wave-

length bowtie antenna and a printed double loop antenna, a new

wideband high-gain antenna element is demonstrated. Due to its

low-profile structure of ~0.05λ0, it is attractive to be used in an

array environment. Experimentally, a series of antenna arrays

operated at 60 GHz are designed and fabricated. They achieve

wide impedance bandwidths covering the 57–64 GHz unlicensed

frequency band. Over this band, the measured antenna gains are

ranged from 14.5–15.5 dBi, 18.3–20.1 dBi and 22.5–25.2 dBi for

4-element, 14-element and 50-element antenna arrays, respectively.

The measured radiation pattern has low cross-polarization level

and low back radiation. The proposed low-profile antenna and

arrays are low-cost in fabrication as they are simply made on a

single-layer printed circuit board.

Index Terms—Low-profile antenna, wideband antenna,

antenna array, 60 GHz radio.

I. INTRODUCTION

ITH the advancement of millimeter-wave (MMW)

technologies, various applications have been proposed,

such as the 39-GHz band for licensed high-speed data links[1],

60-GHz band for unlicensed short range data links [2], 77-GHz

band for automotive radar [3], 94-GHz band for imaging radar

[4], and 71–76, 81–86, 92–95 GHz bands for point-to-point

high bandwidth communication links. For these applications,

the high free space loss and strong atmospheric absorption limit

the distance of communications. Thus, high-gain antennas are

normally required to mitigate the attenuation of such

high-frequency electromagnetic radiation.

Recently, many antennas and arrays with good directional

property were proposed in [5]–[15] for the unlicensed 57–64

GHz frequency band due to many attractive applications

including high definition multimedia interface, high definition

video streaming, high-speed internet, and wireless gigabit

Ethernet. Most of these designs are made of multi-layer

substrates which increase antenna complexity and

manufacturing costs, regardless of using any fabrication

techniques such as printed circuit board (PCB), liquid crystal

Manuscript received Nov. 2, 2013. This work was supported in part by the

Research Grants Council of the Hong Kong SAR and CityU Strategic Research

Grant. [Project No. CityU 9041677 and SRG 7008113]

The authors are with the Department of Electronic Engineering and the State

Key Laboratory of Millimeter Waves, City University of Hong Kong, Hong

Kong (phone: 852-97152234; e-mail: [email protected]).

polymer (LCP) and even low-temperature co-fired ceramic

(LTCC). Among those antennas, Yagi antenna is a good

solution for high gain applications [5], [6]. In [6], the method of

placing stacked Yagi directive elements on a 4 × 4 patch

antenna array fed by a substrate integrated waveguide (SIW)

network realized a high gain and low side-lobe performance.

Slot antenna array also exhibits high-gain property [7]–[9]. The

use of backed cavity as reflector and radiating element

enhancing antenna gain and impedance bandwidth was reported

in [7]. The plate-laminated slot array excited by a

hollow-waveguide corporate-feed achieved a high gain of over

32 dBi [8]. In 2011, Grid array antennas at 60-GHz band were

first proposed by Zhang, et al. [11]. The antenna achieved a

maximum gain of 17.7 dBi [11]. In addition, based on cavity

array, horn antenna, magneto-electric dipole and tapered slot,

many millimeter-wave antennas with good performances were

designed [12]–[15].

For practical use, antennas that are low in fabrication cost and

low in profile are highly desirable. Microstrip patch antenna is a

competitive choice. Several designs on metamaterial structures

or superstrate enable a patch element to achieve high gain at

60-GHz band [16]–[18]. However, these techniques need

multi-layer fabrication, and therefore lose the low-cost

advantage of microstrip antenna. Array of patch elements can be

used for realizing high gain. The microstrip line fed microstrip

antenna array is a single-layer structure, and hence low in

fabrication cost, but suffers from narrow bandwidth [19].

Techniques are available to enhance the bandwidth of

microstrip antennas but multi-layer structures are unavoidable,

including using L-probe feed [20], stacked patches [21], U-slot

patch [22] and aperture coupled feed [23].

In this paper, we present a new unidirectional radiating

element consisting of a planar reflector-backed one-wavelength

bowtie and a double-loop antenna. Design of high gain antenna

arrays based on this antenna element is also investigated. These

antenna array prototypes are fabricated by using a single-layer

printed circuit board technology and designed to operate at

60-GHz band. They have a low profile of 0.05λ0 (λ0 is the

wavelength referring to 60GHz) and achieve wide impedance

bandwidths and high gains. The design process, broadband

characteristic and radiation pattern for single element are

elaborated in Section II. Three antenna arrays of 4-element,

14-element and 50-element are investigated in Section III.

A Low-Profile Unidirectional Printed Antenna

for Millimeter-Wave Applications

Mingjian Li and Kwai-Man Luk, Fellow, IEEE

W

mailto:[email protected]




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II. ANTENNA ELEMENT

A. Design Process

Practical applications at millimeter wave usually require

high-gain unidirectional radiation antennas. If we design a

millimeter-wave antenna array in a single-layer structure, the

dielectric substrate must be properly chosen for minimizing the

insertion loss of the feeding network and assuring the validity of

using microstrip line at millimeter wave. Too thin substrate

gives large conductor loss and too thick substrate introduces

large radiation loss [24]. In this paper, Duroid 5880 substrate is

chosen as its thickness = 0.254 mm (~0.05λ0, λ0 is the

wavelength at 60 GHz in free space), dielectric permittivity εr =

2.24, metal thickness t = 1/2 oz and loss tangent tanδ = 0.004 at

60 GHz [25]. On this substrate, 46.5–170 ohm microstrip lines

can be achieved practically (line width 0.035–0.89 mm) at 60

GHz. Hence, we need an antenna which possesses wideband

and low-profile characteristics at the same time. Microstrip line

fed microstrip antenna has a low profile but suffers from a

narrow bandwidth. A conventional half-wavelength dipole

antenna has a wide bandwidth, but it should be placed above a

reflector with a distance of about λ/4 for achieving a reasonable

performance.

Fig. 1(a) shows a trapezoidal microstrip patch antenna which

is excited at its edge. This antenna is very narrow in bandwidth

as no bandwidth enhancement technique is employed [20]–[23].

Fig. 1(b) shows a reflector-backed one-wavelength bowtie

antenna which consists of two portions, the upper dipole arm

and the lower dipole arm. The upper arm is operated as a

microstrip line fed trapezoidal microstrip patch antenna which

is identical to the antenna shown in Fig. 1(a). The lower arm,

placed opposite to the upper arm, is operated as another

trapezoidal microstrip patch antenna. This arm is excited by a

microstrip-line (MSL) to coplanar-waveguide (CPW) transition

which also feeds the upper arm at its output end. This transition,

composed of two sections including a tapered section and a

straight section (Cw = 0.2mm, gap = 0.03mm), ensures the 1λ

bowtie antenna with a relatively wide impedance bandwidth. As

shown in Fig. 1(c), the reflector-backed one-wavelength bowtie

antenna is loaded with two 1λ loops. The two loops, working as

the conventional double-quad or bi-quad antenna [26], are

connected in parallel to the bowtie antenna for broadening the

antenna impedance bandwidth further. The dimensions of the

proposed antenna element are summarized in TABLE I.

B. Broadband Characteristic

Fig. 2 shows the input impedances of the three antennas

shown in Fig. 1. The trapezoidal microstrip patch antenna

resonates at around 50 GHz with a very large Re (Z11). It can be

easily matched to 50 ohm but will be narrowband owing to its

single resonance. The reflector-backed one-wavelength bowtie

antenna has two electrical resonances at around 51 GHz and

56.5 GHz which are caused by the upper and lower dipole arms,

Excitation/2

Excitation

MSL-CPW Transition

1

(a) (b)

Excitation

Cw

MSL-CPW

Transition

Bottom

LayerTop

Layer

W50

D2

W

S1

L1

D3

S3

D1S2L2

1 Loops

(c)

Fig. 1. Antenna design process. (a) Perspective view of the trapezoidal

microstrip patch antenna, (b) perspective view of the reflector-backed

one-wavelength bowtie antenna, (c) top view of the loop-loaded

reflector-backed one-wavelength bowtie antenna.

TABLE I

DIMENSIONS FOR THE PROPOSED ANTENNA

Parameter D1 D2 D3 L1 L2

Value(mm) 3.58

1.00λ 2.7

0.76λ 1

0.28λ 3.08

0.86λ 1.98

0.55λ

Parameter S1 S2 S3 W

Value(mm) 1.5

0.42λ 0.28

0.08λ 4.1

1.15λ 0.1

0.03λ

λ is one electrical wavelength in Duroid 5880 substrate at 60 GHz.

Fig. 2. Input impedances of the trapezoidal microstrip patch antenna,

reflector-backed one-wavelength bowtie antenna and loop-loaded reflector-backed one-wavelength bowtie antenna.




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respectively. The two arms, operated as two trapezoidal patches,

have different resonant frequencies due to their different

feeding methods. From 50 to 65 GHz, the Re (Z11) and Im (Z11)

of the bowtie antenna vary substantially from 18 to 187 ohm and

-60 to 86 ohm, respectively. The loop-loaded reflector-backed

one-wavelength bowtie antenna possesses three resonances at

around 52 GHz, 56 GHz and 63 GHz. Like the bowtie antenna,

the first two resonances are from the bowtie arms and the third

resonance is introduced by the loaded 1λ loops. The loops,

paralleled with the bowtie, reduce the magnitudes of the Re (Z11)

and Im (Z11) below 59 GHz. Meanwhile, the input impedance

above 59 GHz is increased because of the third resonance

introduced. Hence, compared with the bowtie antenna, this

loop-loaded bowtie antenna element has more stable input

impedance with Re (Z11) of 26–95 ohm and Im (Z11) of -25–50

ohm from 50 to 65 GHz.

C. Radiation Pattern

Fig. 3 shows a simulated radiation pattern of the loop-loaded

dipole antenna at 60 GHz. The maximum gain is about 10 dBi in

the broadside direction. The radiation pattern in the E-plane is

slightly asymmetrical and the cross-polarization level in the

H-plane is high, over -15 dB, which are due to the separation in

one arm of the bowtie to make space for the microstrip-line to

coplanar-waveguide transition. To justify this argument, a

loop-loaded electric dipole antenna excited at its center (without

the MSL to CPW transition) is examined as shown in Fig. 4. It

demonstrates that symmetrical radiation patterns in both

principle planes are achieved. Since the cross-polarization

levels are lower than -40 dB in both planes, the x-pol curves

cannot be shown in the figure.

III. ANTENNA ARRAYS

A. Array Geometries

Fig. 5(a) shows the 4-element antenna array (D3 = 1.4 mm, S1

= 1.9 mm) which adopts the parallel feeding method. This

method suffers from an asymmetrical radiation pattern with a

slightly high cross-polarization level because of the radiation

loss from the feed lines and the element asymmetrical geometry

caused by the MSL to CPW transition.

Fig. 5(b) shows the 14-element antenna array (D3 = 1.4 mm,

S1 = 1.9 mm, L1 = 2.78 mm and L2 = 1.68 mm). It adopts the

hybrid series/parallel feeding method. This method has smaller

frequency sensitivity of the radiation pattern than a purely series

feeding method and therefore achieves a wider gain bandwidth.

The reason is that nearly each frequency dependent microstrip

line segment in the network can find a counterpart in which the

current is in 180° phase difference. Meanwhile, compared with

the parallel feeding method, the series/parallel feeding method

reduces microstrip lines used in the network when exciting an

array with a given number of elements [24], [27]. Thus, this

method has lower insertion loss.

Fig. 5(c) shows the 50-element antenna array which also

adopts the hybrid series/parallel feeding method. Each element

Screws

Feed

point

Antenna fixture

Duroid

5880

15mm

Screws

Feed

point

Antenna fixture

Duroid

5880

20mm

(a) (b)

Duroid5880

Feedpoint

T-Junction Shift

Screw

35mm

Line 1

Line 2

Line 3

Line 4

Line 5 (2 line)

Junction shift

Antenna fixture

/2

line

1

line (~0.80)

Line 6 (2 line)

W100

Ref. 1

Ref. 2

Unconnected

element

Adjacent

elements

Oppesite

elements

(c)

Fig. 5. Top and side views of the proposed antenna arrays. (a) 4-element array,

(b) 14-element array, (c) 50-element array.

Fig. 3. Radiation pattern of the loop-loaded reflector-backed one-wavelength

bowtie antenna at 60 GHz.

Excitation

Fig. 4. Loop-loaded reflector-backed one-wavelength bowtie antenna excited

at its center and its radiation pattern at 60 GHz.




4

is through a 100 ohm impedance transformer (W100 = 0.2mm) to

increase the antenna output impedance. And then it is connected

to its opposite neighboring elements through λ/2 71 Ω lines

(Line 1, 2, 3 & 4), so that the signals at Ref. 1 and Ref. 2

reference planes are 180° apart, which is vital for achieving a

broadside radiation beam and suppressing the radiation losses

due to the element asymmetry geometry, as mentioned in

Section II-C. This also means that the adjacent elements are

joined through 1λ lines (Line 1, 2, 3 & 4), which makes the

element spacing equals to ~0.8λ0 (λ0 is the wavelength at 60

GHz in free space). The Line 2 and Line 3 are responsible for

feeding the middle 28 elements. And the Line 1 and Line 4 feed

the upper and lower 22 elements. Notice that the Line 1, 2, 3 & 4

do not function as impedance transformers because of λ/2 lines

between opposite neighboring elements [25]. The Line 5 and

Line 6 with 2λ are responsible for connecting the Line 1 & 2 and

Line 3 & 4, respectively. The junctions in the middle of the Line

2 and Line 3 are shifted upwards and downwards respectively

for keeping a length of 2λ for the Line 5 & 6, so that all elements

can be excited in phase. The junctions of the Line 2 & 3 joined

to the feed point through λ/4 50 Ω impedance transformers (W50

= 0.7mm) and tapered lines for impedance transformation. The

feed point is positioned at the lower side of the substrate for the

sake of confirming 180° phase difference at the junctions of the

Line 2 & 3. It can be observed that most of the elements are

connected together at the edges of the loops for reducing the

element spacing to ~0.8λ0. The connection between adjacent

elements has no influence on the element operation. The reason

is that the main electromagnetic radiation is from the radiating

slots of the bowtie arms. Although some part of the radiation is

from the loops, especially at higher frequencies, the adjacent

elements are in phase and therefore the connection between

them will not affect the element radiation. The unconnected

elements are not joined to their adjacent elements for leaving

enough space occupied by the vertical lines (such as Line 5 & 6).

This 50-element array, printed on the single-layer Duroid 5880

substrate, is mounted on an aluminum antenna fixture (thickness

= 1.5 mm) by using four metal screws (M1). A V-band

connector (SHF: KPC185F302) and a glass bead (SHF: GB185)

are assembled together and launched at the back of the antenna

fixture. The inner conductor of the connector is connected to the

array feed network at the feed point, as shown in Fig. 5. In

practice, the three proposed arrays may be integrated into a

60-GHz MMIC or silicon CMOS system directly so that the

antenna fixture is not a compulsory part.

B. Array Performances

All simulations were implemented by EM simulation

software Ansoft HFSS. In simulation, the setups for the

substrate and metal are referred to [25] (εr = 2.24, tanδ = 0.004,

ρcopper = 5.8 × 107 S/m). And the measurements on impedance

bandwidth, gain and radiation patterns were accomplished by a

millimeter wave band Agilent E8361A Network Analyzer and

an in-house far-field millimeter-wave antenna measurement

system which was also employed in [14]. It is noted that this

system has been updated so as to broaden the measurable

elevation angle range to ±90°. The details on the measurement

setup have been introduced in [14].

Fig. 6 shows the simulated and measured SWRs of the three

proposed arrays. The measured impedance bandwidths of the

4-element, 14-element and 50-element arrays (SWR ≤ 2) are

24.2% (51.8 to 66.1GHz), > 24% (55 to 70 GHz) and > 16.7%

(56.7 to 67 GHz), respectively, which all cover 57–64 GHz

band. Fig. 7 shows the simulated and measured broadside gains

of the proposed arrays. The measured 3-dB gain bandwidths of

the 4-element, 14-element and 50-element arrays are 20.9%

(54.3 to 67 GHz), 18.9% (56.4 to 68.2 GHz) and 12.5% (57 to

64.6 GHz), respectively. For the sake of the series/parallel

feeding method, the gain bandwidth tends to decrease, as the

number of antenna elements increases [27]. The measured peak

gains for the three arrays are 15.5dBi at 60.2GHz, 20.1dBi at

61GHz and 25.2 dBi at 58.4 GHz. The overlapped 3dB gain

(a)

(b)

(c)

Fig. 6. Simulated and measured SWRs. (a) 4-element array, (b) 14-element

array, (c) 50-element array.

Fig. 7. Simulated and measured gains of the 4-element, 14element and

50-element antenna arrays.




5

bandwidth and the impedance bandwidth for the 4-element,

14-element and 50-element arrays is 19.6% (54.3 to 66.1 GHz),

18.9% (56.4 to 68.2 GHz) and 12.5% (57 to 64.6 GHz),

respectively. Simulations are in relatively good agreement with

results obtained from experiments. Fig. 8 shows the simulated

and measured radiation patterns of the 50-element antenna array.

Over the whole operating frequency band, the measured

radiation pattern exhibits a cross-polarization level less than -30

dB, front-to-back ratio larger than 31 dB and the first side-lobe

level less than -9 dB. Both the measured and simulated results

agree very well. By applying the Tai and Pereira equation [28],

the antenna directivity can be evaluated. The approximated

directivity at 60 GHz is 26.5 dBi, and the corresponding

radiation and aperture efficiencies are 63.7% and 72.5%,

respectively.

Photos of the array prototypes with 4 elements, 14 elements

and 50 elements are shown in Fig. 9. The key data of our works

and other arrays for 60-GHz applications is summarized in

TABLE II. It is noted that our proposed low-cost low-profile

printed antenna arrays, fabricated by using single-layer PCBs,

achieve wide impedance bandwidth, high gain, and high

radiation and aperture efficiencies.

TABLE II

KEY DATA OF ANTENNA ARRAYS FOR 60GHZ APPLICATIONS.

Ref. Type No. of

Layer

No. of

Element Size (mm3)

Impedance

Bandwidth

3dB Gain

Bandwidth

Max Gain

(dBi)

Aperture

Efficiency

Radiation

Efficiency

[6] Yagi (PCB) 6 16 28×24×2.4 10.5% 7% 18 n.a. n.a.

[8] Slot (Plate-laminated) 22 256 75×76×6.6 7.9% >7.9% 33 88.7% >70%

[9] Slot (PCB) 1 144 30.7×30.7×0.508 4.1% >4.1% 22 41.2% 68%

[11] Grid (LTCC) 3 60 15×15×0.6 18.7% 17.2% 17.7 59.9%* n.a.

[12] Cavity (LTCC) 20 64 47×31×2 17.1% >17.1% 22.1 49.8% 44.4%

[20] Patch (LTCC) 10 16 14.4×14.4×1 29% 18.3% 17.5 n.a. n.a.

14-element Loop-loaded dipole (PCB) 1 14 20×20×0.254 22.1% 18.9% 20.1 71.9% 69.7%

50-element Loop-loaded dipole (PCB) 1 50 35×35×0.254 >16.7% 12.5% 25.2 72.5% 63.7%

The aperture efficiency and radiation efficiency are the measured values at the operation frequency of each antenna (60 GHz for our works).

* Aperture efficiency was calculated from simulated 90% radiation efficiency.

E-Plane H-Plane

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

57 GHz

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

60 GHz

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

-40

-30

-20

-10

0

0

30

60

90

120

150

180

210

240

270

300

330

-40

-30

-20

-10

0

64 GHz

Fig. 8. Simulated and measured radiation patterns of the 50-element antenna

array at 57 GHz, 60 GHz, and 64 GHz.

(a)

Feed point

V-band connectorSHF: KPC185F302

Copperground

Antenna fixture

(b) (c) (d)

Fig. 9. Photos of the antenna array prototypes. (a) Top view of all proposed

arrays, (b) backside view of the fabricated PCB for 50-element array, (c)

backside view of the 50-element array with antenna fixture, (d) side view of

the 50-element array with antenna fixture.




6

IV. CONCLUSION

A new printed loop-loaded reflector-backed one-wavelength

bowtie antenna has been presented. This element has a low

profile of ~0.05λ0 and stable input impedance at the same time.

Based on this element, a series of low-cost single-layer antenna

arrays were designed and fabricated at 60 GHz. They have wide

impedance bandwidths covering 57–64 GHz and high gain

properties. The unidirectional radiation patterns exhibit low

cross-polarization and back radiation levels. The measured

results of the fabricated prototypes are in good agreement with

simulated results. In addition, the proposed antenna array made

of single-layer printed circuit board is very low cost in

fabrication. They are excellent candidates for various low-cost

millimeter-wave systems.

ACKNOWLEDGMENT

The authors would like to thank Mr. Kung Bo Ng for helping

with the antenna measurements. This work was supported in

part by the Research Grants Council of the Hong Kong SAR and

CityU Strategic Research Grant. [Project No. CityU 9041677

and SRG 7008113]

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[19] B. Biglarbegian, M. Fakharzadeh, D. Busuioc, M.-R. N.-Ahmadi, and S.

S.-Naeini, “Optimized microstrip antenna arrays for emerging

millimeter-wave wireless applications,” IEEE Trans. Antennas and

Propagation, vol. 59, no. 5, pp. 1742–1747, May 2011.

[20] L. Wang, Y.-X. Guo, and W.-X. Sheng, “Wideband high-gain 60-GHz

LTCC L-probe patch antenna array with a soft surface,” IEEE Trans.


[21] T. Seki, N. Honma, K. Nishikawa, and K. Tsunekawa, “Millimeter-wave

high-efficiency multilayer parasitic microstrip antenna array on teflon

substrate,” IEEE Trans. Antennas and Propagation, vol. 53, no. 6, pp.

2101–2106, Jun. 2005.

[22] H. Sun, Y.-X. Guo, and Z. Wang, “60-GHz circularly polarized u-slot

patch antenna array on LTCC,” IEEE Trans. Antennas and Propagation,

vol. 61, no. 1, pp. 430–435, Jan. 2013.

[23] D. Liu, J. A. G. Akkermans, H.-C. Chen, and B. Floyd, “Packages with

integrated 60-GHz aperture-coupled patch antennas,” IEEE Trans.

Antennas and Propagation, vol. 59, no. 10, pp. 3607–3616, Oct. 2011.

[24] E. Levine, G. Malamud, S. Shtrikman, and D. Treves, “A study of

microstrip array antennas with the feed network,” IEEE Trans. Antennas

and Propagation, vol. 37, no. 4, pp. 426–434, Apr. 1989.

[25] D. Liu, B. Gaucher, U. Pfeiffer, and J. Grzyb, Advanced Millimeter-wave

Technologies, Antennas, Packaging and Circuits. New York: Wiley,

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[26] S. Ahmed and W. Menzel, “A novel planar four-quad antenna,” Antennas

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[27] S. Demir, “Efficiency calculation of feed structures and optimum number

of antenna elements in a subarray for highest G/T,” IEEE Trans.


[28] C. A. Balanis, Antenna Theory: Analysis and Design. New York: Wiley,

2005.

Mingjian Li (S’10) received the B.Sc. (Eng.)

degrees in electronic and communication

engineering from City University of Hong Kong in

2010, where he is currently pursuing Ph.D. degree.

His recent research interests include wideband

antennas, millimeter-wave antennas and arrays, base

station antennas, circularly-polarized antennas and

small antennas.

Mr. Li received the Honorable Mention at the

student contest of 2011 IEEE APS-URSI Conference

and Exhibition held in Spokane, US. He was

awarded the Best Student Paper Award (Second Prize) in the 2012 IEEE

International Workshop on Electromagnetics (IEEE iWEM2012) held in

Chengdu, China.




7

Kwai-Man Luk (M’79–SM’94–F’03) was born and

educated in Hong Kong. He received the B.Sc. (Eng.)

and Ph.D. degrees in electrical engineering from The

University of Hong Kong in 1981 and 1985,

respectively.

He joined the Department of Electronic

Engineering, City University of Hong Kong, in 1985

as a Lecturer. Two years later, he moved to the

Department of Electronic Engineering, Chinese

University of Hong Kong, where he spent four years.

He returned to the City University of Hong Kong in

1992, and is currently Chair Professor of Electronic Engineering and Director

of State Key Laboratory in Millimeter waves (Hong Kong). He is the author of

three books, nine research book chapters, over 290 journal papers and 220

conference papers. He has received five US and more than 10 PRC patents. His

recent research interests include design of patch, planar and dielectric resonator

antennas, and microwave measurements.

Prof. Luk is a Fellow of the Chinese Institute of Electronics, PRC, a Fellow

of the Institution of Engineering and Technology, UK, a Fellow of the Institute

of Electrical and Electronics Engineers, USA and a Fellow of the

Electromagnetics Academy, USA. He is Deputy Editor-in-Chief of PIERS

journals. He was a Chief Guest Editor for a special issue on “Antennas in

Wireless Communications” published in the PROCEEDINGS OF THE IEEE in July

2012. He was Technical Program Chairperson of the 1997 Progress in

Electromagnetics Research Symposium (PIERS), General Vice-Chairperson of

the 1997 and 2008 Asia-Pacific Microwave Conference (APMC), General

Chairman of the 2006 IEEE Region Ten Conference (TENCON), Technical

Program Co-chairperson of 2008 International Symposium on Antennas and

Propagation (ISAP), and General Co-chairperson of 2011 IEEE International

Workshop on Antenna Technology (IWAT). He received the Japan Microwave

Prize at the 1994 Asia Pacific Microwave Conference held in Chiba in

December 1994, and the Best Paper Award at the 2008 International

Symposium on Antennas and Propagation held in Taipei in October 2008. He

was awarded the very competitive 2000 Croucher Foundation Senior Research

Fellow in Hong Kong and the 2011 State Technological Invention Award (2nd

Honor) of China.

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