1&1 DX Green Mode PWM Controller 计，外壳不需要开散热孔， … · DRV Source resistance RSRC - 10 30 DRV Sink resistance RSINK í 6 19 ... the average inductor current

. DXGreen Mode PWM Controller

Datasheet Rev. 3.0 - 1 -

1

8

1

GENERAL DESCRIPTION The series are high performance fixed frequency for Off-Line and DC-to-DC converter

applications offering the designer a cost effective solution with minimal external components. These integrated circuits feature a trimmed oscillator for precise duty cycle control, a temperature compensated reference, high gain error amplifier, current sensing comparable, and a high current totem pole output ideally suited for driving a power MOSFET. Also included are protective features consisting of input and reference under voltage lockouts each with hysteria, cycle-by-cycle current limiting, programmable output dead time, and a latch for single pulse metering. Difference between members of this series is the under-voltage lockout thresholds. The has UVLO thresholds of 16 V (on) and 10 V (off), ideally suited for off-line converters. The is offered in SOP-8 and DIP-8packages.

FEATUREProprietary frequency shuffling technology for improvedEMI performance Leading edge Blanking on current sense input.Internal synchronized slope compensation.Extended burst mode control for improved efficiency andminimum standby power designLow VDD start up current and low operating current.Cycle-by-Cycle Current LimitingPower on Soft-start, Programmable CV and CCRegulationVDD under Voltage Lockout with Hysteresis (UVLO),OVP, OCP, OLP, Clamp VDDTrimmed Oscillator Discharge Current for PreciseDuty Cycle ControlAdjustable Switching Frequency up to 500 kHzInternally Trimmed Reference with under voltageLockoutHigh Current Totem Pole OutputUnder voltage Lockout with hysteresisLow Start-Up and Operating CurrentUp to 28V VCC Operation+500 mA/–800 mA Source / Sink Capability

TYPICAL APPLICATIONS Power Supplies for PC Silver BoxesTV/Set-Top Box Power SuppliesBattery ChargerFlyback and Forward Converter

ORDERING INFORMATION

Part Number Package Type Production Flow

. DX SOP-08L -40 C to +85 C*

*Design Guarantee: The device is guaranteed to meet the specifications from 0 C to 70 C. Specifications over the –40 C to 85 C operatingtemperature range are assured by design, characterization and correlation with the statistical process controls

OFFLINE CONTROLLER

PIN CONNECTIONS

1

MARKING DIAGRAM

Specific Device Code

DX: Assembly Location

XX: Year

XX: Work Week

电动车充电方案NCN5201DX，MAX：70V3A,无风扇设计，外壳不需要开散热孔，效率90,咨询186 8245 1525



TYPICAL APPLICATION SCHEMATIC

BLOCK DIAGRAM



PIN FUNCTION DESCRIPTION Pin No. Function Description

1 GND Connect this pin to the pre converter ground.

2 CS Monitors the primary current and allows the selection of the ramp compensation amplitude.

3 RT A resistor connected to ground fixes the switching frequency.500 kHz is possible.

4 DRV This pin connects to the MOSFET gate

5 GND The controller ground pin

6 VCC DC power supply pin

7 PG_OK/REF5V

The Pin voltage is high (5 V) when the PWM stage is in a normal, steady state situation and low otherwise. This signal serves to “inform” the downstream converter that the PFC stage is ready and that hence, it can start operation.

8 FB Feedback input pin. PWM duty cycle is determined by voltage level into thispin and current-sense signal level at Pin 2.

ABSOLUTE MAXIMUM RATINGSRating Symbol Value Unit

Total Power Supply and Zenger Current (ICC+IZ) 30 mAPower Supply voltage, VCC pin voltage Vcc 28 VOutput Current, Source or Sink (Note 1) IO 1 AOutput Energy (Capacitive Load per Cycle) w 5 uCurrent Sense and Voltage Feedback Inputs Vin -0.3 to +5.5 VMaximum Power Dissipation @ TA=25°C PD 862 mWThermal Resistance Junction to Air R JA 1 °C/Maximum Power Dissipation @ TA=25°C PD 1.25 WThermal Resistance Junction to Air R JA 1 °C/Operating Junction Temperature TJ +150 °CLead Temperature (Soldering, 10sec) TLEAD +300 °CStorage Temperature Range Tstg -65 to + 150 °C

ELECTRICAL CHARACTERISTICS (VCC=15V, RT=10k, CT=3.3nF, TA=TLOW to THIGH

Parameter Symbol Conditions Min. Typ. Max. UnitFEEDBACK SECTION

Open loop feedback voltage FB pin=open VFBOL - 5 - V

FB pin maximum current FB Pin= GND IFB 1 mA

ZFB_IN -- Input Impedance 10 KInternal Diode forward voltage -- Vf 0.75 V



CURRENT SENSE SECTIONGain GV -- 2.85 3 3.15 V/VCurrent Sense Voltage Threshold VI(MAX) VILIM 0.9 1 1.1 VPower Supply Rejection Ratio PSRR 25V - 70 - dBInput Bias Current IBIAS - - -3 -10 APropagation Delay (Current Sense Input to gate turned off) - tILIM - 150 300 ns

OSCILLATOR SECTION Oscillator Frequency f TJ = 25 C 47 52 57 kHzFrequency Change with Voltage 25V 0.05 1 %Oscillator Amplitude VOSC 1.6 VP-PMaximum operating frequency f 500 kHz

PWM SECTIOND(Max) 76 80 84 %

PGOK/REF5V Line Regulation PG 25V - 6 20 mV

VPG OKH PG VREF TJ = 25 C, IREF = 1mA 4.9 5 5.1 V Icap_ref - 5 10 - mA

DRIVE OUTPUTISINK = 20mA - 0.08 0.4 VLow Output Voltage

VOL

ISINK = 200mA - 1.4 2.2 VISOURCE = 20mA 13 13.5 - V

High Output Voltage VOH

ISOURCE = 200mA 12 13.0 VRise Time tR TJ = 25 C, CL= 1nF - 45 150 ns Fall Time tF TJ = 25 C, CL= 1nF - 35 150 ns

DRV Source resistance RSRC - 10 30DRV Sink resistance RSINK 6 19

SUPPLY SECTION AND VCC MANAGEMENTStartup threshold at which driving pulses are authorized

VCC increasing

VCC(on) 14.5 16 17 V

Min. Operating Voltage (After Turn On)

VCC decreasing

VCC(off) 8.5 10 11.5 V

Hysteresis between VCC(on) and VCC(min)

VCC(HYS) - 6 - V

TOTAL STANDBY CURRENTStart-Up Current IST - - 0.45 1 mA

Operating Supply Current ICC(OPR) Vpin3=Vpin2=ON - 14 17 mA

Tthat is synchronized with the PWM clock to the control voltage, the I perturbation will decrease to zero on succeeding cycles. This compensation ramp(m3) must have a slope equal to or slightly greater than m2/2 for stability. With m2/2 slope compensation, the average inductor current follows the control voltage yielding true current mode operation. The compensating ramp can be derived from the oscillator and add to either the Voltage Feedback or Current Sense inputs .


first case, Pin7 is in high state and lowotherwise.


APPLICATION INFORMATIONIntroduction

The hosts a high performance current

mode controller specifically developed to drive

power supplies designed for the ATX and the

adapter market:

Current Mode operation: implementing peak

current mode control topology, the circuit offers

supplies.

Adjustable switching frequency: a resistor

to ground precisely sets the switching frequency

between 50 kHz and a maximum of 500 kHz.

There is no synchronization capability.

Internal frequency jittering: Frequency

jittering softens the EMI signature by spreading out peak energy within a band 5% from the

center frequency.

Wide Vcc excursion: the controller allows

operation up to 28 V continuously and accepts

transient voltage up to 30 V during 10 ms with

IVCC < 20 mA.

standby power represents a difficult exercise

when the controller requires an external, lossy,

resistor connected to the bulk capacitor. The

to be less than

100 _A maximum, helping the designer to reach

a low standby power level.

Shutdown: if an external transistor brings the

FB pin down, the controller is shut down, but all

internal biasing circuits are alive. When the pin is

released, a

Internal ramp compensation: a simple

resistor connected from the CS pin to the sense

resistor allows the designer to inject ramp

compensation inside his design.

PG_ OK REF: the circuit detects when the

circuit it is in a startup or fault condition. In the

Pin7 serves to control the downstream converter operation in response to the PFC state.

Current Sensing and leading edge blankingCycle-by-Cycle current limiting is offered in

current mode PWM control. The switch current is detected by a sense resistor into the sense pin. An internal leading edge blanking circuit chops off the sense voltage spike at initial MOSFET on state due to snubber diode reverse recovery so that the external RC filtering on sense input is no longer required. The current limit comparator is disabled and thus cannot turn off the external MOSFET during the blanking period. PWM duty cycle is determined by the current sense input voltage and the FB input voltage.

: Thehigh to permit a large energy storage in a small VCC capacitor value. This helps to operate with a

together with a small VCC capacitor, will not hamper the To further reduce the standby power, the current of the controller is extremely low, below 15 m refore beconnected to the bulk capacitor or directly to the mains input voltage to further reduce the power dissipation. The first step starts with the calculation of the VCC capacitor which will supply the controller when it operates until the auxiliary winding takes over. Experience shows that this time t1 can be between 5 ms and 20 ms. If we consider we need at least an energy reservoir for a t1 time of 10 ms, the VCC capacitor must be larger than:

Let us select a 4.7 _F capacitor at first and we were too optimistic for the time t1. The VCC capacitor being known, we can now evaluate the charging current we need to bring the VCC voltage from 0 to


Datasheet Rev. 3.0- 6 -

the VCCon of the IC, 18V typical. This current

e

lowest mains (85 V rms) to be less than 3 s (2.5 s

for design margin):

If we account for the 15uA that will flow inside

the controller, then the total charging current

delivered by the uA.

network to the mains

that the

will be the smallest when VCC reaches the

VCCon of the controller:

To make sure this current is always greater than

49uA,

be extracted:

This calculation is purely theoretical, and

assumes a constant charging current. In reality,

the take over time can be shorter (or longer!) and

it can lead to a reduction of the VCC capacitor.

Hence, a decrease in charging current and an

sistor, thus reducing

the standby power. Laboratory experiments on

the prototype are thus mandatory to fine tune the

converter. If we chose the 413k resistor as

suggested by Equation 4, the dissipated power

at high line amounts to:

(eq.5)

Now that the first VCC capacitor has been

selected, we

not disappear when in

deep that

refreshing pulses are likely to be widely spaced,

inducing a large ripple on the VCC capacitor. If this

ripple is too large, chances exist to touch the VCC

min and reset the

sequence. A solution is to grow this capacitor but it

will obviously be detrimental to the

The option offered in Figure 1 elegantly solves this

potential issue by adding an extra capacitor on the

auxiliary winding. However, this component is

separated from the VCC pin via a simple diode.

You therefore have the ability to grow this capacitor

as you need to ensure the

controller without jeopardizing the

and standby power. A capacitor ranging from 22 to

47uF is the typical value for this device. One note

on the start-up current. If educing it helps to

improve the standby power, its value cannot fall

below a certain level at the minimum input voltage.

Failure to inject enough current (30uA) at low line

will turn a converter in fault into an auto-recovery

mode since the SCR won’t remain latched. To build

a sufficient design margin, we recommend to keep

at least 60uA flowing at the lowest input line (80

Vrms for 85V minimum for instance).



Auto :

supply experiences a severe overloading

situation, an internal error flag is raised and

starts a countdown timer. If the flag is asserted

longer than 100ms, the driving pulses are

stopped and the VCC pin slowly goes down to

around 10V. At this point, the controller

due to

the resistive starting network. When VCC

reaches VCCon, the controller attempts to

absence of the fault. If

the fault is still there, the supply enters another

If the fault has

cleared, normal operation.

Slope Compensation: The includes an internal ramp

compensation signal. This is the buffered

oscillator clock delivered only during the on time.

Its amplitude is around 5V at the maximum

means

used to cure sub harmonic oscillations in

Continuous Conduction Mode (CCM) operated

signal will be disconnected from the CS pin,

Current mode converters. These oscillations take

place at half the switching frequency and occur

only during CCM with a

50%. To lower the current loop gain, one usually

injects between 50% and 100% of the inductor

downslope. Figure 3 depicts how internally the

ramp is generated. Please note that the ramp

during the off time.

Figure 2. ated for Faults Longer than 100 ms

Figure 1. The Startup Resistor Can Be Connected to the Input Mains for Further Power


Oscillator timing capacitor, CT, is chargedby


In the E controller, the oscillator ramp features a

clock operates at a 65kHz frequency, then the

available oscillator slope corresponds to:

In our flyback design, let’s assume that our

primary inductance Lp is 770uH, and the SMPS

delivers 19V with a Np:Ns ratio of 1:0.25. The

Sp is thus given

by:

(eq.7)

Given a sense resistor of 330m , the above

current ramp turns into a voltage ramp of the

following amplitude:

Slope Compensation:

(eq.8)

If we select 50% of the downslope as the required

amount of ramp compensation, then we shall inject

a ramp whose slope is 17 mV/_s. Our internal

compensation being of 208 mV/_s, the divider ratio

(divratio) between Rcomp and the internal 20k

resistor is:

The series compensation resistor value is thus:

(eq.10)

A resistor of the above value will then be inserted

from the sense resistor to the current sense pin.

We recommend adding a small capacitor of 100

pF, from the current sense pin to the controller

ground for an improved immunity to the noise.

Please make sure both components are located

very close to the controller.

Figure 3. Inserting a Resistor in Series with the Current Sense Information Brings Ramp Compensation and

(eq.6)

(eq.9)



PG_Vref through RT and discharged by an

internal current source. During the discharge

time, the internal clock signal blanks the output

to the low state. Selection of RT and CT

therefore determines both oscillator frequency

and maximum duty cycle. Charge and discharge

times are determined by the formulas:

tc = 0.55 RT CT

.

(eq.11)

Frequency, then, is: f=(tc + td)-1

(eq.12)

Figure 4. Oscillator Dead Time & Frequency

在现有的PCBA上，改动IC和IC周边几个电阻和电容即可实现。

联系人：赖生电话： 186 8245 1525 QQ/微信：896 3737 11

电动车充电方案NCN5201DX，MAX：70V3A,无风扇设计，外壳不需要开散热孔，效率90。

注：MAX70V 10A的即将上市，敬请期待



PACKAGE OUTLINES

PACKAGE DIMENSIONSSOP 8

Small Outline PackageUNIT : inch



Shipping packingSOP-8 tape & Reel:

1Pc / device

2500 devices / Reel

12 Reel / Carton(30,000Pcs / Carton)

Label Label



EMBOSSED TAPE AND REEL DATA CARRIER TAPE SPECIFICATIONS

DIMENSIONS

Tape B1 Max

(Note 1)D D1 E F K P0 P2 R Min T Max W Max

4.55 mm 1.5 + 0.1 mm 1.0 Min 1.75 0.1 mm 3.5 0.05 mm 2.4 mm 4.0 0.1 mm 2.0 0.1 mm 25 mm 0.6 mm 8.3 mm0.0 (0.039 ) (0.069 (0.138 Max (0.157 (0.079

(0.059 + or0.004 0.5 mm

Min

8 mm (0.179 )

(0.020 )

0.002 ) (0.094 )(0.98 ) (0.327 )

8.2 mm 1.5 mm 5.5 0.05 mm 6.4 mm 30 mm 12 0.30 mmMin (0.217 Max (0.470 12 mm (0.323 )

0.002 ) (0.252 ) 0.012 )

12.1 mm 7.5 0.10 mm 7.9 mm 16.3 mm(0.295 Max16 mm (0.476 )0.004 ) (0.311 )

(0.642 )

20.1 mm 11.5 0.1 mm 11.9 mm 24.3 mm(0.453 Max24 mm (0.791)

0.0)

(0.060 )

0.004 )

0.004 ) (0.468 )

0.004 ) 0.002 )

(1.18 )

(0.024 )

(0.957 )



REEL DIMENSIONS

A B C

Reel Tape Min Max Min Max Min Max

D E

178.0 (7.01) 16.0 (0.63) 50.0 (1.97) 6.5 (0.26) 7.5 (0.30) 16.4 (0.65) 18.4 (0.72) 22.4 (0.88) 19.4 (0.76)

330.0 (12.99) 12.0 (0.47) 178.0 (7.01) 4.5 (0.18) 5.5 (0.22) 12.4 (0.49) 14.4 (0.57) 18.4 (0.72) 15.4 (0.61)

330.0 (12.99) 56.0 2.20 150.0 (5.91) 10.0 (0.39) 11.0 (0.43) 56.4 (2.22) 58.4 (2.30) 62.4 (2.46) 59.4 (2.34)

330.0 (12.99) 44.0 (1.73) 100.0 (3.94) 10.0 (0.39) 11.0 (0.43) 44.4 (1.75) 46.4 (1.83) 62.4 (2.46) 47.4 (1.87)

330.0 (12.99) 32.0 (1.26) 100.0 (3.94) 10.0 (0.39) 11.0 (0.43) 32.4 (1.28) 34.4 (1.35) 38.4 (1.51) 35.4 (1.39)

330.0 (12.99) 24.0 (0.94) 60.0 (2.36) 9.5 (0.37) 10.5 (0.41) 24.4 (0.96) 26.4 (1.04) 30.4 (1.51) 27.4 (1.08)

330.0 (12.99) 16.0 (0.63) 6.5 (0.26) 7.5 (0.30) 16.4 (0.65) 18.4 (0.72) 22.4 (0.88) 19.4 (0.76)

330.0 (12.99) 12.0 (0.47) 4.5 (0.18) 5.5 (0.22) 12.4 (0.49) 14.4 (0.57) 18.4 (0.72) 15.4 (0.61)

330.0 (12.99) 8.0 (0.31) 50.0 (1.97) 2.5 (0.10) 3.5 (0.14) 8.4 (0.33) 9.9 (0.39) 14.4 (0.57) 10.9 (0.43)

178.0 (7.01) 12.0 (0.47) 50.0 (1.97) 4.5 (0.18) 5.5 (0.22) 12.4 (0.49) 14.4 (0.57) 18.4 (0.72) 15.4 (0.61)

178.0 (7.00) 8.0 (0.31) 50.0 (1.97) 2.5 (0.10) 3.5 (0.14) 8.4 (0.33) 9.9 (0.39) 14.4 (0.47) 10.9 (0.43)

330.0 (12.99) 8.0 (0.31) 50.0 (1.97) 4.0 (0.16) 5.0 (0.20) 8.4 (0.33) 9.9 (0.39) 14.4 (0.57) 10.9 (0.43)

178.0 (7.00) 8.0 (0.31) 50.0 (1.97) 4.0 (0.16) 5.0 (0.20) 8.4 (0.33) 9.9 (0.39) 14.4 (0.57) 10.9 (0.43)

Documents

1&1 DX Green Mode PWM Controller 计，外壳不需要开散热孔， … · DRV Source resistance RSRC - 10 30 DRV Sink resistance RSINK í 6 19 ... the average inductor current